W094/00943
`
`21
`
`PCT /US92/05317
`
`4.
`
`A radio transceiver, comprising:
`A) a transmitter, comprising:
`i) a Nyquist filter;
`il) differential encoder means coupled to the
`5 Nyquist filter for filtering an input information signal to
`cause selective rotation of a phase value of a modulated
`signal by a predetermined amount; and
`iii) frequency modulator means operably
`coupled to the differential encoder means for outputting
`the modulated signal; and
`B) a receiver, which receiver does not have a
`Nyquist filter, for receiving and properly demodulating
`both:
`
`1 o
`
`15
`
`i) a constant envelope signal occupying a
`first spectral bandwidth; and
`ii) a non~constant envelope signal occupying a
`second spectral bandwidth, wherein the first spectral
`bandwidth is different from the second spectral
`bandwidth.
`
`Apple Exhibit 1010
`
`DEF0002242
`
`IPR2020-00036 Page 02521
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`Ex. 2012
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`Page 2521
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`

`

`\VO 94/00943
`
`22
`
`PCT /US92/05317
`
`5.
`
`A radio communication system, comprising:
`A) a first plurality of transceivers, each
`transceiver comprising:
`i) a transmitter, comprising at least a
`5 Nyquist filter and transmitting a constant envelope
`signal occupying a first spectral bandwidth;
`ii) receiver means, which receiver means
`does not have a Nyquist filter, for receiving and properly
`demodulating both:
`a) a constant envelope signal occupying
`the first spectral bandwidth; and
`b) a non-constant envelope signal
`occupying a second spectral bandwidth, which
`second spectral bandwidth is different than the
`first spectral bandwidth;
`B) a second plurality of transceivers, each·
`
`1 O
`
`15
`
`comprising: 1r a transmitter, comprising at !east a
`
`Nyquist filter and transmitting a non-constant envelope
`signal occupying the second spectral bandwidth; and
`ii) receiver means, which receiver means
`does not have a Nyquist filter, for receiving and properly
`demodulating both:
`a) a constant envelope signal occupying
`the first spectral bandwidth; and
`b) a non-constant envelope signal
`occupying the second spectral bandwidth;
`such that- transceivers from the first plurality of
`transceivers can compatibly communicate with
`transceivers from the second plurality of transceivers.
`
`20
`
`25
`
`30
`
`DEF0002243
`
`IPR2020-00036 Page 02522
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`Page 2522
`
`

`

`!.ll w --~
`N -.:::::,
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`
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`FIG.1A
`
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`
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`
`-PRIOR ART-
`FIG.2A
`
`FREQUENCY
`CARRIER
`EXP (jwt)
`
`MODULATION
`
`I Jiol"'{RC~
`
`200
`
`207
`
`206
`
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`204
`
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`
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`
`202
`
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`4-1..EVEL'f
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`
`-PRIOR ART-
`FIG.1B
`
`131
`
`z-1 I-'
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`
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`
`DATA
`
`125
`
`BIT·RECOVERY
`GRADIENT
`STOCHASTIC
`
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`
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`
`1J2
`
`129
`
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`
`128
`
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`
`127
`
`126
`
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`
`, 101 1 ~ Ki }i'•'ffi!t) I (cid:141) MODULATION
`
`10J
`
`102
`
`DATA
`
`4-LEVEL ~
`
`IPR2020-00036 Page 02523
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`Page 2523
`
`

`

`8 c
`
`th w ....
`0
`......
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`EXP (jwt}
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`
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`
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`
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`FIG.2B
`
`225
`
`~229
`
`233
`
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`
`DAT A
`STOCHASTIC ~ 4 LEVEL
`
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`
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`
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`
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`f
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`
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`
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`I
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`I
`
`IPR2020-00036 Page 02524
`
`Rembrandt Wireless
`Ex. 2012
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`Page 2524
`
`

`

`th
`<:::::>
`N ......
`e rJj
`"ti g
`
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`0
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`
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`
`..
`
`FREQUENCY (KHz)
`
`10
`i
`
`5
`I
`
`Ill
`
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`
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`
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`
`FIG.3C
`
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`
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`
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`6.25 KHz
`LESS THAN ~
`I
`
`-
`
`I BANDWIDTH
`
`5.76 KHz
`-.1 MORE THAN
`
`PASS
`
`-607
`
`-40 I
`
`-20J
`
`0 l
`
`AMPLITUDE
`
`(dB)
`
`FIG.4
`
`353 L ____ __J
`
`l......--r-----..........JI
`I
`
`z-1
`
`1.
`
`I .._111111111111111 I . J5 7
`~ J5: 1--=-+ 356 : -f 7 STOCHASTIC t~ 4-LEVEl
`
`.----
`
`GRADIENT
`
`I
`
`ANO .
`
`Ill--__.--~ L
`
`J61
`
`I J59
`-I DUMP I BIT RECOVERY
`
`TAN -
`
`IF FILTER
`
`!
`
`LOOSE
`I
`J52
`
`J51
`
`MODULATION I
`
`IPR2020-00036 Page 02525
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`Ex. 2012
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`Page 2525
`
`

`

`..
`
`W094/00943
`
`PCT /US92/053 l 7
`
`4/4
`
`1
`
`0.8
`
`0.6
`
`0.4
`
`I
`
`0.2.,j..
`
`I
`
`.5 A
`
`-1
`
`-0.5
`
`0,5
`
`i
`
`F IG.5
`
`F IG.5C
`
`-3
`
`i
`-2
`
`-1
`
`1
`
`2
`
`DEF0002247
`
`IPR2020-00036 Page 02526
`
`Rembrandt Wireless
`Ex. 2012
`Apple Inc. v. Rembrandt Wireless Technologies, LP, IPR2020-00034
`Page 2526
`
`

`

`INTERNATIONAL SEARCH REPORT
`
`lntem11.ti0Ml 11pplicatio11 No.
`PCTiUS!l2/05317
`
`A.
`CLASSIFICATION OF SUBJECT MA'I'TER
`:
`. H04L 27/10; H04L 27/18
`IPC(S)
`:
`US CL
`37~9
`Acoordillg to Internatiow.l. Patent CwsifiCJ1tlo11 (IPC) or to bo!h MOOW cl.u&ification md IPC
`B.
`FJELDS SEARCHED
`Mini.mu.,n documentation !it::.im:hcd (cwsiikation iystem followed by clllss.iftcation symbols)
`: U.S. CL 375/8, «; 45, Sl,52, 58, 60,99; 455/49,50, 73, 74, 93, 142; 329/JOO, 304; 37o/123
`
`U.S.
`
`Documentation ~earohed oilier tlw3 mini.mum documentation to !he exJ:ent !tmt !ilich documents are included in the field~ searched
`
`Electronic dala. bue ooMulted during ilie internatiorutl sem:h (ll!lffle of data base and, where p.mctlcable, search terms used)
`
`C. DOCUMENTS CONSIDERED TO BE RELEVANT
`
`-,
`
`Category*
`
`Citation of docume!lt, with indication, where appropriate, of the relevant pusllges
`
`Relevant to claim No.
`
`,X
`
`A
`
`A
`
`A
`
`US,A, 4,720,839 {FEHER) 19 lANUARY 15188 (SEE FIGURE lB, COL 2 LINES 29-42)
`
`1-3
`
`US,A, 4,601,04B (RYAN) 15 JULY 1986
`
`US,A, 4,731,796 (MASTERTON) 15 MARCH 1988
`
`'!JS,A, 4,843,615 (DA VIS) 27 JUNE 1989
`
`1-5
`
`1-5
`
`1-5
`
`(cid:143) Further documents are llited in the contim.1.&tion of Box C.
`.
`
`·r
`
`(cid:143) See patent family lillnex.
`
`hi!tt d -l'!Jblim«I wr the im.<mOOO!!.lll filillg llm <>r pri<>rity
`dw> QIIII l&!!t i i : !~ .,,it!, ti.. o;,plil:ooo!! l!ul cit!!d I<> ""'1ot'llW'.ld !ho
`prir,,;q,lo '" lOOlfy umerlyii,gtll<i iowmlioo
`
`s~ eatq<1m11 of ernod d~ :
`~ddim,og lb<, s:"""""21 -
`.,f1l,o o,t .,.,i,;..--i,;. _.,.,.,.idm,!
`l<>l>oportof~~
`·x· ~ • .,f ~ ""°"""""; 11,,:: ol,,im,od mvmruro "'"'"''""
`"""'""....! """el "'=ti,., """"itl•m<I !a mvolv• "" ""'"""'" ""P
`-i;,,,,1~ pw,!iilheli 00 "1 afltt li>o ~ fW!IJf <lsto
`"E"
`,,,...,, 11,,,,l~i, IIOk"1 .ioo..
`'L" d - whk:h ""'Y ll,..,..,. dOlll,t,, "" pmrity c!&im(o) ,,, wii>oh io
`~ - { ... ~ )
`eitoo w ...ixl>liol> fl>e pw,lic<woo d&!ie <>f ~ oi!OOioo or <>11><,r
`•y• ~ o f~ ~~ li>e ~ involl!ion <mnot be
`""""i,!im,l !a ;,,.,,.1v., ... mv"""""" ""'I' "''""' Ibo, ,l""""""' ;.
`<:ms!>"""' willl (Ill< ,., more O!hor ~ o l - , -i:. cs:m,biru,lion
`"O'" d -~ 1<> ,m ol'lll <ili,o::~. Ule, emi1im® or Olher
`~ ®"KIWI IQ • I""'""" wllod ;,. 11,;c o,t
`"""""
`d""""""'pw,liffl<,l ,,.;.,rw i l l< ,~ ru.., ~ !o,,t....,. ~
`·.st· d -~ <>f lh•"""" l"'1':0>l fllmi1y
`qbo: priorityolote eloimoc!
`Date of mailing of the mtei:natiorial ~ea.ch report
`Date of the actual oomplction of the international search
`i
`21/0CT 1992
`
`"A"
`
`•p-
`
`10 SEPTEMBER 1992
`
`Name and ms.il.lng llddrcsi of the ISA/
`Comm.illlliooor of lPA!cllll &lld Tll11<i111>M&W
`llk>i:PCT
`Wl!ioogton, D.C. 20231
`-
`Facsimile No. NOT APPLICABLE
`Form PCTfISA/210 (second sheet)(My 19112},l,
`
`.. _..m.," ~r~
`
`SAFOUREK, E EDICT
`
`....,__
`
`Telephone No.
`
`(7{13) 305-4364
`
`/
`
`DEF0002248
`
`IPR2020-00036 Page 02527
`
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`Page 2527
`
`

`

`PCT
`
`WORLD f.N'IF.1.J..F.CTUAL PROPERTY ORGANJ7ATION
`faternruional Bureau
`
`IN'TERNATIONAL APPLICATION PUBLISHED 1.JNDER THE PATENT COOPERATION TREATY (PCT)
`WO 94/19892 .
`
`(51) InterRlatiom!I Patent ClassmcatfoRl 5 :
`H04L 27/10, 27/14, 27/1.6, 27/22, H04B
`1100, 1/02, 1/66, 1116, 7/00
`
`Al
`
`(11) lnternational Publication Number:
`
`(43) lnternational Publication Date:
`
`i September 1994 (Ol.09.94)
`
`(21) International ApplicatioRl Number:
`
`PCTlUS94/00580
`
`(!11) Designatoo States: AU, BR., CA, JP, KR, VN.
`
`Published
`With international search report.
`
`(22) International Filing Date:
`
`14 January 1994 (14.01.94)
`
`(30) Priority Data:
`08/018,589
`
`17 Feb!1JMY 1993 (17.02.93)
`
`us
`
`(71) AppliCl!Dt: MOTOROLA INC. [US/US]; 1303 East Algonquin
`Roa.d, Schaumburg, Il, 601% (US).
`
`(72) Inventor: WILSON, A1M, L.; 3720 Alder Drive, Hoffman
`Estates, IL 60195 (US).
`
`(74) Agents: PARMEI...EE, Steven, G. et al.; Motorola, Inc.,
`futellectuai Property Department/SLL, 1303 East Algonqllin
`Road, Schaumburg, IL 601% (US).
`
`(54} Tit.le: MULTIPLE-MODIJLA.TION COMMUNICATION SYSTEM
`
`4-LEVEL FM TRANSMITTER
`DSP
`FREQUENCY
`MODULATOR
`
`CLASS C
`
`101
`
`LINEAR AM TRANSMITTER
`DSP
`UNEARIZER
`
`107
`
`COMMON RECEIVER
`RECEIVE
`FRONT
`END
`
`DIGITAL
`RECEIVER
`
`DSP
`
`113
`
`115
`
`117
`
`(S7) Aoomu:t
`
`A multiple-modulatiolll communication system mdudes a transmitter (201, 203, 205, 2ff7, 209, 211, 213, 215, 217, 219) lhmt
`modulates and l!'lmsmi;;; communication sigw;l~ modulated by a fifflt modulation technique (201, 203, 205, 207} and comm!ink:atio11 signals
`modulawd by a second modulmio1.1 technique (211, 213, 215, 217). The first modulation tecimique and !he second modulation t.eclmique
`a.re different. The communication system also includes a receiver (221, 223, 225, 2Z7, 229, 231) Cl!pJ!ble or receiving tb.e i::oou:mmication
`signals modumted by the first modmatlon tedmlque and !he c=unication sigo.als modulated by the i!CCOnd modulation ieclmique and
`demod!!lllting the commlll!ication sigools.
`
`DEF0002939
`
`IPR2020-00036 Page 02528
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`Page 2528
`
`

`

`FOR TIIE PURPOSES Of" lNFORMA1'ION ONLY
`
`Codes used to identify Sr.at.es party to the PCT on the front pages of pai:nplllets publfohlug :lnt.emational
`applications under we PCT.
`
`Al!ll!rill
`AT
`Amtr.U..
`AU
`RB
`Blirt)wog
`!.IE
`Be!gim,>
`Bwlciru, F.,,c,
`Bl!
`Btilgw
`BG
`BJ
`llfflil,
`!.IR
`Brazil
`BY
`&WU!!
`CA ~
`Coooot Am,cm Repll!llic
`CF
`(.,'G
`CollJ!O
`Switz,erl&ld
`CH
`C&led'h-.,ire
`CI
`CM
`C&!neEIXlli
`Qrlru,
`CN
`cs
`Cucl:!oolovo
`CZ
`C:r~Rcpol,lic
`DE
`Ge:rm&!!y
`DK ~
`Sp&n
`ilS
`FI
`Fillw><I
`Frm::e
`FR
`GA
`C,o.ron
`
`Unro>d Klngd001
`GB
`GE ~
`GN
`Girl=
`GR. Gr=
`mr
`tilq:llf!I
`IB
`~ I i
`IT
`Itoly
`r"!Wl
`JP
`KE
`Kteya
`KG K~
`KP ~ c l'oopte's Rq,llhlic
`of Kore&
`R,,pl!l>lic c,f'.Kore,.
`Im
`KZ
`Kml:ll-
`u L l~
`LK Sri~
`LU
`LwiffllOO!.ll11
`LV
`LiltVi.l
`MC M=
`MD
`Rq,lllliic of MoidoVll
`MG
`M&/l&gil!IQ!l
`ML
`M>li
`Mrogo,lill
`MN
`
`M&mtmi&.
`MR
`MW
`Mmwl
`Nig«
`NE
`NL N~.i.
`NO
`Noiw•y
`NewZeili!Kl
`NZ
`l!"L
`PolJm!I
`Pr
`l'ortug,tl
`RO
`&ow.'lil>
`IRU
`Rlilioi.on 1',,i!m,ric,n
`s~
`SD
`SE
`Swedffl
`SI
`Sloveru.R
`SK
`Sloru:i&
`SN
`Ser.lepl
`a...d
`'ID
`ro
`Togo
`TJ
`T•jil:istm
`TT
`Tonidod""'1T~
`UA
`Ul::raille
`us
`Ur.ired si.w,,i <lf Am.me&
`uz u~
`VN
`Vic!N~
`
`•.
`'(cid:141)
`
`DEF0002940
`
`IPR2020-00036 Page 02529
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`Ex. 2012
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`Page 2529
`
`

`

`WO 94/19892
`
`PCT /US94/00580
`
`1
`
`5
`
`MULTIPLE-MODULATION COMMUNICATION SYSTEM
`
`Field of the Invention
`
`This invention relates to radio frequency signals, including but
`not limited to transmission and reception of amplitude modulated
`(AM) and frequency modulated (FM) signals.
`
`Background of the Invention
`
`A radio communication system permits transmission of
`information between a transmitter and a receiver. A radio
`frequency (RF) channel permits transmission of information
`between the transmitter and the receiver. By combining the
`information with an RF electromagnetic wave of a particular
`frequency, i.e., modulating the information signal onto a carrier
`frequency, the resultant modulated information signal may be
`transmitted through free space to a receiver. Various modulation
`techniques (e.g., amplitude (AM), frequency (FM), phase, and
`composite modulation) are known to combine the information
`signal with an electromagnetic wave. Communication units,
`such as portable radios, mobile radios, and base stations, contain
`transmitters and/or receivers.
`A linear AM transmitter does not have as much coverage
`area, i.e., the signal does not travel as far, as an FM transmitter at
`the same peak transmit power level because the average envelope
`size of an AM transmission varies below the maximum output
`level, whereas the average envelope size of an FM transmission is
`constant at the maximum output level. An FM transmitter,
`
`10
`
`15
`
`2J
`
`2.15
`
`35
`
`DEF0002941
`
`IPR2020-00036 Page 02530
`
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`Page 2530
`
`

`

`WO 94/19892
`
`PCT /US94/0ll580
`
`2
`
`however, uses more energy to transmit at the same power level as
`a.Tl AM transmitter, and hence the FM transmitter will more
`quickly drain the battery of a portable transmitter.
`Accordingly, there is a need for a transmitter which has the
`low power characteristic of an AM transmitter while retaining the
`advantage of coverage area of an FM transmitter.
`
`Brief Description of the Drawings
`
`FIG. 1 shows an FM transmitter, an M1 transmitter, and a
`common receiver in accordance with the invention.
`FIG. 2 shows a detailed FM transmitter, a detailed AM
`transmitter, and a detailed common receiver in accordance with
`the invention.
`
`Description of a Preferred Embodiment
`
`The following describes an apparatus for and method of
`transmitting communication signals with a single transmitter
`and receiving the same signals with a single receiver. Additional
`communication range is obtained when transmitting FM signals.
`More efficient battery performance is achieved when transmitting
`linear AM signals. A single transmitter transmits both AM and
`FM signals. A single receiver capable of differentiating phase
`differences demodulates either AM or FM signals. Only one
`receiver is necessary, and there is no need to inform the receiver of
`what type of modulation was performed on the transmitted signal.
`In the preferred embodiment, FM modulators have 12.5 kHz
`channels and linear AM modulators have 6.25 kHz channels. The
`receiver can be the same in either case. The form of modulation
`used in the present invention is called QPSK-c. This modulation
`technique is discussed in detail in U.S. Application No. 07/629,9Bl
`titled "Multi-Modulation Scheme Compatible Radio" filed on behalf
`
`5
`
`10
`
`15
`
`25
`
`30
`
`35
`
`DEF0002942
`
`IPR2020-00036 Page 02531
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`Ex. 2012
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`Page 2531
`
`

`

`WO 94/19892
`
`PCT iUS94/0058U
`
`5
`
`10
`
`15
`
`2.5
`
`3
`
`of Alan L. Wilson et al. on December 19, 1990, which information
`is enclosed herein by reference. QPSK stands for Quaternary
`Phase Shift Keying. QPSK-c, where the c stands for compatible, is
`a linear differential form of QPSK that is AM and FM compatible.
`It is possible to transmit with a higher average power using FM,
`and hence increased coverage area is obtained for the signal than
`when AM is used. An Ml transmitter, however, consumes less
`power and hence is a more efficient user of a portable radio's
`battery charge or power than an FM transmitter. When using
`QPSKftc modulation, 4ftleve1 FSK (Frequency Shift Keying} is used
`in FM transmissions and DftQPSK (Differential QPSK) is used in
`AM transmissions. Switching from AM to FM yields higher
`average power, and hence increased coverage area for the signal,
`at the cost of battery charge. Thus range is enhanced and greater
`coverage is obtained for the same radio, or communication unit,
`when such coverage is desired. Conversely, switching from FM to
`AM when extended range is not necessary conserves battery
`charge. In the present invention, the communication unit
`changes its type of modulation and thus is more quickly responsive
`to such a change. This is accomplished by, inter alia, an x/(sin x)
`filter, where x :::: 1t fT in the preferred embodiment, and a phase
`angle integrator for the exponential function.
`One part of FIG. 1 shows a conventional four~level FM
`transmitter. Information to be transmitted enters a digital signal
`processor (DSP) 101. The DSP 101 processes the information and
`sends it to frequency modulator 103 which passes the information
`to power amplifier (PA) 105 which is rated class C. As shown in
`FIG. 1, a class C four-level FM transmitter transmits a constant
`envelope.
`A conventional linear AM transmitter is also shown in FIG.
`1. Information to be transmitted is processed in DSP 107 and
`output to a conventional linearizer 109, the output of which is input
`to a class AB power amplifier 111. As seen in the diagram, an AM
`signal has a non-constant envelope. The average signal power of
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`

`

`WO 94/19892
`
`PCT /US94/00581l
`
`4
`
`an AM signal is less than the average signal power of an FM
`signal having the same peak envelope size.
`Also shown in FIG. 1 is a common :receiver which may
`receive information from both four-level FM transmitter and
`linear AM transmitters. The common receiver has a front-end
`receiver 113, a digital receiver 115, and a digital signal processor
`117 that processes the information into data or audible speech. A
`linear AM transmitter has a time¥varying amplitude that is
`reduced for high frequency deviation. Note that DSP 101, DSP 107,
`and DSP 117 also perform functions other than those shown.
`Throughout the specification and drawings, the DSP as shown
`may be a DSP 56001 available from Motorola., Inc.
`FIG. 2 shows a detailed implementation of the transmitters
`and :receiver of f'IG. 1. An FM transmitter, yielding 4¥level FSK
`data, is shown by blocks 201, 203, 205 and 207. 4-level data is input
`to a raised-cosine filter 201 which is a splatter filter of the Nyquist
`raised-cosine finite impulse response type with splatter filter
`transition ratio alpha= 0.2, as is known in the a.rt, The FM
`transmitter includes a differential encoder comprised of blocks 203
`and 205. An fT/sin(n fT) filter 203 and an integrator 205 comprise
`the differential encoder. In the preferred embodiment, the
`integrator 205 is a simple integrator that uses the modulo 2r.:
`property of the phase to avoid overflowing, as is known in the art.
`The output of integrator 205 is the phase 0 of the 4ulevel input
`signal. A detailed description of one implementation of the raised(cid:173)
`cosine filter 201 and 11: fT/sin(n: IT) filter 203 follows in the next
`paragraph. Phase modulator 207 takes the phase f,!I and modulates
`it, creating a complexuvalued result that is designated e.1~. The
`output, e.1~, of phase modulator is input to switch 209.
`The cascaded filter implementation of the Nyquist
`raised-cosine filter 201 and the rr IT/sin(it IT) filter 203 may be
`implemented as follows. Let H(w) equal the frequency response of
`an ideal Nyquist raised cosine filter. The normalized corner
`frequency is 1 radian/second, and the normalized symbol time
`(denoted by T) is 11: seconds, and
`
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`10
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`

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`
`PCT /liS94f{l0580
`
`5
`
`H(oo) = 1
`
`for 1 - a.;?; wl
`H(oo) = l + lcoJn{lffi - l + a))
`2 2 1
`2a
`for l +a< I wl.
`H(ro) = 0
`
`for 1 -a <lwl :s; l + o.
`
`5
`
`The impulse response, h(t), of the filter is found with the inverse
`Fourier transform, and noting that H(w) is an even function:
`
`h(t) = -1.. f °" H(w)ei00tdw = .l1ro H(fu) cos(wt) dw
`11+a
`11-a.
`11+a
`cos(u1t) dro + .l
`2n:
`1
`·O:
`
`2x
`
`·""
`
`= 1
`re
`
`O
`
`cos(ffit) dw + ..1.
`2n
`
`X
`
`0
`
`1
`·U
`
`cojn{@-l +a,)} cos(u1t) d(1)
`i
`2a
`
`10
`
`15
`
`25
`
`Using the identity cos(x) cos(y) = 0.5 cos(x+y) + 0.5 cos(x-y) and
`performing the integration:
`
`h(t'"" sin[(l-a)t] + sin[(l+a)t] - sin[(l-a)t]
`'
`m
`2m
`sin[n+(l+a.)t] - sin((l-o:)t]
`4,rr/...1.L + t)
`+
`·,20.
`
`sin[n-(l+a.)t] + sin[(l--a)t]
`4.J..1L -t)
`.
`+
`'12a
`
`Using the identity sin(n+x) = -sin(x), regrouping terms, and then
`using the identity sin(x+y) + sin{x-y) = 2 sin(x) oos(y):
`
`h(t) = n sin[(l+a.)t] + sin[(l-a.)t] = 1t sin(t) cos(at) .
`/ ..1L)2
`8o.2t
`a,2
`\2a..
`
`The filter function h(t) can be sampled at discrete time intervals to
`realize the Nyquist raisedacosine finite impulse response filter 201.
`The shaping filter, f(t), is derived as follows, where F(ro) is the
`frequency response of the shaping filter, T is the symbol time
`which equals 208.333 µsec for 9600 bits per second which equals 1t
`seconds for the normalized system used in H above, and
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`

`WO 94/19892
`
`PCT /US94fll0580
`
`5
`
`10
`
`15
`
`25
`
`6
`
`F<rn) =
`roT/2
`,
`sin(rnT/2)
`
`for all frequencies.
`
`The frequency :range of interest for F(rn) is -1.2n < wT < 1.2rc, which
`is the frequency range covered by the Nyquist filter H(w) when the
`roll~off factor a= 0.2, In order to find a suitable impulse response,
`the function F will be approximated with a Fourier series of cosine
`terms, and the result will be transformed to the time domain.
`A time interval to approximate F is first selected to be
`±1.33333:n:, because it must exceed ±1.21t and be less than ±2n
`because there is a singularity in F at roT::::2'.ll:. The Fourier series
`expansion follows, where :xis the normalized frequency:
`
`""
`F(x) = . me = fo + I fkCO"/ ~nk; ) where .x = IT = .wT,
`''h.33333
`2n
`
`k:::l
`
`srn(mc:)
`213
`
`fo = 0.75[
`
`F(x) dx, and
`
`2/3
`
`fk = 1.51213
`
`2/3
`
`F{x) co~ 211:kx } dx
`1.33..133
`
`for k > 0.
`
`These integrals are easily evaluated numerically. The first twelve
`terms appear in the following table.
`
`k
`
`0
`1
`2
`3
`4
`5
`
`fk
`
`1.35697
`-0.4839
`0.189043
`-0.0982102
`0.0594-481
`-0.0390059
`
`k
`
`6
`7
`8
`9
`10
`11
`
`fk
`
`0.0281791
`-0.0210304
`0.0162746
`eQ.0129571
`·0.0105541
`~0.00875928
`
`Performing the inverse Fourier transform on the series as follows:
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`

`WO 94/19892
`
`PCT/US94/0l.l580
`
`7
`
`2n ·""
`
`2rc
`
`•00
`
`k,::J
`
`1.33333 ,
`
`ftt) = ..1.. f"' F(w)dCiltdw = -=1---f °" (ro + }: fkco~ 2ruor ) ') eJ(()t dro
`=·-1-(ro&:t)+ f f~.8(0.75kT)+ f fko(-0.75kT))
`
`2n: \
`
`bl 2
`
`k=l 2
`
`;
`
`5
`
`10
`
`15
`
`25
`
`where .S(t) represents the Dirac delta function. Sampling at 8
`samples per s:ymbol yields non-zero samples and 0.75 x 8 = 6
`sample intervals. The middle or 0th sample has amplitude f o, and
`the remaining samples have amplitudes fk/2 for k:::::±1, ±2, ±3, ...
`Cascading the previously computed h(t) with ft:t) yields the filters
`necessary for an FM n/4 DQPSK-c transmitter, as used in the
`preferred embodiment of the present invention. Although the
`above implementation is shown in band-limited form, band.(cid:173)
`limiting is optional and is not required for the present invention.
`The AM t:ransmitter1 yielding D-QPSK data, is comprised of
`blocks 211,213,215, and 217. Four level data having levels of± n/4
`and ± 3n:/4 enters a differential encoder comprised of a summer
`211 and a delay 213. The output of this differential encoder enters a
`phase modulator 215, where the output of the phase modulator 215
`has complex components I and Q at one sample per symbol. I
`represents the in~phase component, and Q represents the
`quadrature component. The output of modulator 215 is input to
`raised cosine filter 217 with alpha = 0.2 where raised cosine filter
`217 is similar to raised cosine filter 201. The output of raised
`cosine filter 217 is input to switch 209. Whichever form of
`transmission is selected, either FM or A.i..'1, the output of that part
`of the transmitter is input to modulator 219, which modulates the
`signal to the carrier frequency w.
`Blocks 211, 213, and 215 each operate at the :rate of one
`sample/symbol or 4800 syrnbolsisecond. Blocks 201 and 217
`interpolate from 1 sample/symbol to N samples/symbol at the
`
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`

`WO 94/19892
`
`PCT fUS9.4/00580
`
`8
`
`output, where N is usually 10 or more, but at least greater than
`one. Blocks 203, 205, and 207 each operate at N samples/symbol.
`For efficiency and to eliminate redundant parts in the
`preferred embodiment, only one class AB PA is used in the
`transmitter, thus the linear Mi transmitter configuration of FIG.
`1 is used to embody the entire transmitter of FIG. 2, blocks 201
`through 219 inclusive. Because the preferred embodiment of the
`present invention uses a DSP, transmitter blocks 201,203,205,207,
`209, 211, 213, 215, 217, and 219 are easily implemented in the DSP
`107 of the linear AM transmitter. Because blocks 201 through 219
`are included in the DSP 107, it is unnecessary to duplicate DSP 101,
`frequency modulator 103, and PA 105. The modulator 219 is also
`implemented in the DSP 107 1 and the output of the modulator 219 is
`input to the linearizer 109 prior to transmission.
`A detailed common receiver is also shown in FIG. 2. In the
`preferred embodiment, the receiver blocks 221, 223, 225, 227, 229,
`and 231 are a.11 implemented in the DSP 117, When the :receiver
`and transmitter are in the same communication unit or radio, one
`or more DSPs may be used to support the functions of DSP 107 and
`DSP 117. A loose IF (intermediate frequency) filter 221, first
`receives a modulated signal. The output of the loose IF filter 221 is
`input to inverse tangent function 223, which is part of a frequency
`demodulator including blocks 223,225 and 227. Blocks 225 and 227
`a.re also part of a differential encoder also including integrate a.11d
`dump filter 229, the function of which is described in detail in the
`following paragraph. The output of block 223 is input to summer
`227 and the positive form of the delayed component is subtracted
`from block 227 as output from block 225. The output of integrate
`and dump filter 229 is input to stochastic gradient bit recovery
`block 231 the output of which is four level data as transmitted
`initially. Stochastic gradient bit recovery is well known in the art.
`Because the receiver is sensitive only to phase, the envelope does
`not matter and both FM and AM transmission may be received
`and properly decoded by this common receiver. Thus, because a
`more powerful AM PA is required than for an FM PA for the same
`
`5
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`

`

`WO 94/19892
`
`PCT fUS94/00580
`
`9
`
`range, a switch of the two modulations temporarily although
`draining more power gains extra (greater) coverage area.
`The impulse response for the integrate and dump filter 22.9 is
`derived below, in a closedufo:rm solution that is expressed in terms
`of the sine integral function Si(x), which is well known in the art.
`A bandulimited integrate and dump filter is achieved when a
`portion of the side lobes are filtered out of the frequency response.
`The portion of the frequency response that is necessary for good
`fidelity in the symbol recovery is in the range u(l + a.)/(2T) Hz to
`(1 + a)/(2T) Hz. Because of a spectral null at J/I' Hz, the response
`is restricted to l!T Hz cutoff. Where H(x) is the frequency response
`of a band~limited integr3:te and dump filter:
`
`H(x):::::: sin(:rtx)
`TeX
`
`H(x) = 0
`
`for Ix I< 1
`forlxl ~ 1.
`
`Where h(t) is the impulse response of the filter H(x), w = 2ror, and
`H(w) is an even function:
`
`h(t) = _J_
`21t
`
`12n
`H(w)eiuli:dw = _l_
`sin(w/2) ~rotdoo
`2:it -2n
`oo/2
`
`""
`
`2.. sin(w/2) cos(oot) dro
`= .l.
`1to (J)
`•
`
`l.( sin[(t+l/2) '"l - sin[(tul/2) rn]) drn
`:: .l
`1t O 00
`
`'"'
`f.
`12:rt
`12n
`(12mt+l/2)
`=; (Si[2n:(t+l/2)J - Si[2n(t-1/2)]) where Si(x) = ix sin(t) .dt._
`
`= 1.
`it
`
`0
`
`sin(v) dy -
`~ y
`
`)
`12n(t-1/2)
`sin(y) dy
`y
`
`0
`
`0
`
`t
`
`5
`
`10
`
`1,5
`
`2.5
`
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`

`WO 94/19892
`
`PCT /US94!00580
`
`10
`
`5
`
`10
`
`15
`
`Although the above implementation is shown in band-limited
`form, bandulimiting is optional and is not required for the present
`invention.
`Hence in the present invention, when it is desired for any
`reason by command or as determined by the radio, the radio will
`automatically switch from AM to FM to gain extra range for a
`particular signal. . The radio or communication unit may also
`receive a signal, such as from a base station or other controlling
`unit including another radio, instructing it to transmit with a
`particular modulation. Similarly, the radio will automaticaHy
`switch from FM to A.'\\1 to gain better battery efficiency. This
`switching takes place in switch 209, which is controlled by a DSP
`in the preferred embodiment.
`Although the preferred embodiment uses QPSK-c
`modulation, a common receiver can still be used for any
`modulation that distinguishes data by phase, i.e., where all the
`constellation points fall on a circle, such as QPSK, D~QPSK, and
`CORPSK (Correlated PSK).
`Although a DSP is used to perform many of the functions of
`the present invention, discrete elements or other programmable
`logic may also be used and will achieve the same effect.
`
`What is claimed is:
`
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`

`

`WO 94/19892
`
`PCTlUS94/0DS80
`
`11
`
`Claims
`
`1. A communication system characterized by:
`
`a transmitter that modulates and transmits communication
`signals modulated by a first modulation technique and
`communication signals modulated by a second modulation
`technique, wherein said first modulation technique and said
`second modulation technique are different; and
`
`a receiver capable of receiving said communication signals
`modulated by said first modulation technique and said
`communication signals modulated by said second modulation
`technique and demodulating said communication signals.
`
`2. The communication system of claim 1, further
`characterized in that said first modulation technique is amplitude
`modulation and said second modulation technique is frequency
`modulation.
`
`3. The communication system of claim 1, further
`characterized in that said first modulation technique is
`differential quaternary phase shift keying a,.'1.d said second
`modulation technique is 4-level frequency shift keying.
`
`4. The communication system of claim l, further
`characterized in that said communication signals modulated by
`said first modulation technique are transmitted when low power
`consumption by said transmitter is desired.
`
`5. The communication system of claim l, further
`characterized in that said communication signals modulated by
`said second modulation technique are transmitted when greater
`signal coverage by said transmitter is desired.
`
`5
`
`10
`
`15
`
`25
`
`3:.l
`
`35
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`

`

`WO 94/19892
`
`PCT lUS!/4/00580
`
`12
`
`6. A communication unit characterized by:
`
`means for modulating communication signals by a first
`modulation technique, producing a first modulated signal;
`
`means for modulating communication signals by a second
`modulation technique, producing a second modulated signal,
`wherein sai<l first modulation technique and said second
`modulation technique are different;
`
`means for selecting between said first modulated signal and said
`second modulated signal, producing a selected signal; and
`
`a transmitter for transmitting said selected