(19) United States
`(12) Patent Application Publication (10) Pub. No.: US 2006/0159120 A1
`(43) Pub. Date:
`Jul. 20, 2006
`Km
`
`US 2006O1591.20A1
`
`(54) METHOD AND SYSTEM FOR RATE
`SELECTION ALGORTHM TO MAXIMIZE
`THROUGHPUT IN CLOSED LOOP
`MULTIPLE INPUT MULTIPLE OUTPUT
`(MIMO) WIRELESS LOCAL AREA
`NETWORK (WLAN) SYSTEM
`(76) Inventor: Joonsuk Kim, San Jose, CA (US)
`Correspondence Address:
`MCANDREWS HELD & MALLOY, LTD
`SOO WEST MAIDSON STREET
`SUTE 34OO
`CHICAGO, IL 60661
`Appl. No.:
`11/061,567
`
`Filed:
`
`Feb. 18, 2005
`
`(21)
`(22)
`
`Related U.S. Application Data
`(60) Provisional application No. 60/593.473, filed on Jan.
`17, 2005.
`
`Publication Classification
`
`(51)
`
`Int. C.
`H04 3/22
`HO4, 3/6
`H04O 700
`
`(2006.01)
`(2006.01)
`(2006.01)
`
`(52) U.S. Cl. ........................... 370/465; 370/437; 370/328
`
`(57)
`
`ABSTRACT
`
`Aspects of a method and system for rate selection algorithm
`to maximize throughput in closed loop multiple input mul
`tiple output (MIMO) wireless local area network (WLAN)
`system are provided and may comprise computing a maxi
`mum number of binary bits to be simultaneously transmitted
`via an RF channel based on signal quality. A modulation
`technique may be selected based on the computed maxi
`mum, communicating feedback information comprising the
`selected modulation technique. Subsequently transmitted
`data may be received via an RF channel which is modulated
`based on the feedback information. Another aspect of the
`method may comprise receiving feedback information com
`prising at least one of a selected modulation technique and
`coding rate via an RF channel, and transmitting Subsequent
`data via said at least one of a plurality of RF channels which
`either modulated, or coded, based on the feedback informa
`tion.
`
`
`
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`100-y
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`O8a
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`110a
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`112
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`114a
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`inverse Fast
`Fourier
`Transfer
`
`Beamforming
`
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`inverse Fast
`Fourier
`transform
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`
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`Digital:Analog
`Conversion. He
`Antenna Front
`Eric
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`Digital Analog
`Conversioni H
`Antenna Front
`End
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`Antenna Front
`End
`DigitalAnalog
`Conversion
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`Antenna Front
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`Digital Analog
`Conversion
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`Beamforming
`U atrix
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`Fast
`Fourier
`Transform
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`Fast
`Fourier
`Transform
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`126a
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`Demapper
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`32
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`Deinterleaver
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`Depuncture
`
`w/ 101
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`
`
`
`
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`Exhibit 1032
`Panasonic v. UNM
`IPR2024-00364
`Page 1 of 21
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`Patent Application Publication
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`Jul. 20, 2006 Sheet 1 of 10
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`US 2006/01591.20 A1
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`Exhibit 1032
`Panasonic v. UNM
`IPR2024-00364
`Page 2 of 21
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`Patent Application Publication
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`Jul. 20, 2006 Sheet 2 of 10
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`US 2006/01591.20 A1
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`Exhibit 1032
`Panasonic v. UNM
`IPR2024-00364
`Page 3 of 21
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`Patent Application Publication
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`Jul. 20, 2006 Sheet 3 of 10
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`US 2006/01591.20 A1
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`Exhibit 1032
`Panasonic v. UNM
`IPR2024-00364
`Page 4 of 21
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`

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`Patent Application Publication Jul. 20, 2006 Sheet 4 of 10
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`US 2006/01591.20 A1
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`Exhibit 1032
`Panasonic v. UNM
`IPR2024-00364
`Page 5 of 21
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`Patent Application Publication Jul. 20, 2006 Sheet 5 of 10
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`Panasonic v. UNM
`IPR2024-00364
`Page 6 of 21
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`Panasonic v. UNM
`IPR2024-00364
`Page 7 of 21
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`

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`Patent Application Publication
`
`Jul. 20, 2006 Sheet 7 of 10
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`US 2006/01591.20 A1
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`
`
`Exhibit 1032
`Panasonic v. UNM
`IPR2024-00364
`Page 8 of 21
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`

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`Patent Application Publication
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`Jul. 20, 2006 Sheet 8 of 10
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`US 2006/01591.20 A1
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`Exhibit 1032
`Panasonic v. UNM
`IPR2024-00364
`Page 9 of 21
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`

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`Patent Application Publication
`
`Jul. 20, 2006 Sheet 9 of 10
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`US 2006/01591.20 A1
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`
`
`Exhibit 1032
`Panasonic v. UNM
`IPR2024-00364
`Page 10 of 21
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`Patent Application Publication
`
`Jul. 20, 2006 Sheet 10 of 10
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`US 2006/01591.20 A1
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`Exhibit 1032
`Panasonic v. UNM
`IPR2024-00364
`Page 11 of 21
`
`

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`US 2006/O 1591.20 A1
`
`Jul. 20, 2006
`
`METHOD AND SYSTEM FOR RATE SELECTION
`ALGORTHM TO MAXIMIZE THROUGHPUT IN
`CLOSED LOOP MULTIPLE INPUT MULTIPLE
`OUTPUT (MIMO) WIRELESS LOCAL AREA
`NETWORK (WLAN) SYSTEM
`
`CROSS-REFERENCE TO RELATED
`APPLICATIONS/INCORPORATION BY
`REFERENCE
`0001. This application makes reference to, claims priority
`to, and claims the benefit of U.S. Provisional Application
`Ser. No. 60/593,473 (Attorney Docket No. 16412US01)
`filed Jan. 17, 2005.
`0002 This application makes reference to:
`U.S. patent application Ser. No.
`(Attorney Docket
`No. 16307US02) filed Feb. 7, 2005.
`U.S. patent application Ser. No.
`No. 16354US02) filed Feb. 7, 2005.
`0003 All of the above state applications are hereby
`incorporated herein by reference in their entirety.
`
`(Attorney Docket
`
`FIELD OF THE INVENTION
`0004 Certain embodiments of the invention relate to
`wireless communication. More specifically, certain embodi
`ments of the invention relate to a method and system for a
`rate selection algorithm to maximize throughput in a closed
`loop multiple input multiple output (MIMO) wireless local
`area network (WLAN) system.
`
`BACKGROUND OF THE INVENTION
`0005. The Institute for Electrical and Electronics Engi
`neers (IEEE), in resolution IEEE 802.11, also referred as
`802.11, has defined a plurality of specifications which are
`related to wireless networking. With current existing 802.11
`standards, such as 802.11(a),(b),(g), which can Support up to
`54 Mbps data rates, either in 2.4 GHz or in 5 GHZ frequency
`bands, the IEEE standards body created a new task group,
`802.1 lin, to support higher than 100 Mbps data rates.
`Among them being discussed are specifications for closed
`loop feedback mechanisms by which a receiving station may
`feedback information to a transmitting station to assist the
`transmitting station in adapting signals, which are sent to the
`receiving station. In closed loop feedback systems, a trans
`mitting station may utilize feedback information from a
`receiving station to transmit Subsequent signals in what is
`called beam forming. Beamforming is a technique to steer
`signals to a certain direction for the receiver to receive it
`more reliably with less noise and interference. Compounded
`with demands for new features and capabilities, various
`proposals for new 802.11n based feedback mechanisms are
`emerging to address the demand for these new features and
`capabilities. For example, there exists a demand for the
`introduction of new capabilities, which may enable a receiv
`ing mobile terminal to feedback pertinent information to a
`transmitting mobile terminal. This feedback of pertinent
`information may enable the transmitting mobile terminal to
`adapt its mode of transmission based upon the feedback
`information provided by the receiving mobile terminal. As
`with any communication system, a major goal is to enable
`the transmitting mobile station to achieve a higher informa
`tion transfer rate to the receiving mobile terminal, while
`
`simultaneously achieving a lower packet error rate (PER).
`Notwithstanding, there are no existing methodologies that
`adequately address these shortcomings and the demand for
`these new features and capabilities in WLANs.
`0006 Further limitations and disadvantages of conven
`tional and traditional approaches will become apparent to
`one of skill in the art, through comparison of Such systems
`with some aspects of the present invention as set forth in the
`remainder of the present application with reference to the
`drawings.
`
`BRIEF SUMMARY OF THE INVENTION
`0007 Certain embodiments of the invention may be
`found in a method and system to increase throughput in
`closed loop multiple input multiple output (MIMO) wireless
`local area network (WLAN) system, substantially as shown
`in and/or described in connection with at least one of the
`figures, as set forth more completely in the claims.
`0008. These and other advantages, aspects and novel
`features of the present invention, as well as details of an
`illustrated embodiment thereof, will be more fully under
`stood from the following description and drawings.
`
`BRIEF DESCRIPTION OF SEVERAL VIEWS OF
`THE DRAWINGS
`0009 FIG. 1 is an exemplary block diagram of a trans
`mitter and a receiver in a MIMO system, in accordance with
`an embodiment of the invention.
`0010 FIG. 2 is an exemplary block diagram of a trans
`mitter with adaptive modulation and a corresponding
`receiver with adaptive demodulation for a MIMO system, in
`accordance with an embodiment of the invention.
`0011 FIG. 3 is an exemplary block diagram of a trans
`mitter with adaptive modulation and coding, and a corre
`sponding receiver with adaptive demodulation and decoding
`for a MIMO system, in accordance with an embodiment of
`the invention.
`0012 FIG. 4 is a graph illustrating exemplary packet
`error rates (PER) versus signal to noise ratio (SNR) for a 1x1
`system, in accordance with an embodiment of the invention.
`0013 FIG. 5 is a graph illustrating exemplary throughput
`as a function of modulation and coding rate selection, in
`accordance with an embodiment of the invention.
`0014 FIG. 6 is a graph illustrating exemplary throughput
`versus SNR for open loop and adaptive systems, in accor
`dance with an embodiment of the invention.
`0015 FIG. 7a is a flow chart illustrating exemplary steps
`for an adaptive coding system, in accordance with an
`embodiment of the invention.
`0016 FIG.7b is a flow chart illustrating exemplary steps
`for an adaptive modulation and coding system, in accor
`dance with an embodiment of the invention.
`0017 FIG. 7c is a flow chart illustrating exemplary steps
`for a transmitter-based adaptive coding system, in accor
`dance with an embodiment of the invention.
`0018 FIG. 7d is a flow chart illustrating exemplary steps
`for a transmitter-based adaptive modulation and coding
`system, in accordance with an embodiment of the invention.
`
`Exhibit 1032
`Panasonic v. UNM
`IPR2024-00364
`Page 12 of 21
`
`

`

`US 2006/01591.20 A1
`
`Jul. 20, 2006
`
`DETAILED DESCRIPTION OF THE
`INVENTION
`0019 Certain embodiments of the invention may be
`found in a method and system for a rate selection algorithm
`to maximize throughput in a closed loop multiple input
`multiple output (MIMO) wireless local area network
`(WLAN) system, which utilizes either adaptive modulation,
`or adaptive modulation and coding in a closed loop system.
`0020. In accordance with an embodiment of the inven
`tion, with regard to channel information, MIMO systems
`may utilize the channel more efficiently. For example, RF
`channels that are characterized by higher signal to noise
`ratios (SNR) may support higher data transfer rates than RF
`channels with lower SNR. Eigen beam forming, or beam
`forming, may be utilized with systems that support the
`exchange of feedback information from a receiver to a
`transmitter (or closed loop systems) to steer beams which
`may enable signal energy to be focused in a desired direc
`tion. Any of a plurality of RF channels which may be utilized
`by a transmitter to communicate with a receiver may be
`referred to as downlink channels, while any of a plurality of
`RF channels which may be utilized by a receiver to com
`municate with a transmitter may be referred to as uplink
`channels.
`0021) Adaptive modulation and coding rate techniques
`may be utilized with beam forming techniques such that a
`plurality of signals, or streams, may be transmitted simul
`taneously that comprise different amounts of data. The
`modulation and/or coding rate may be chosen per stream
`efficiently, with either or both capable of being modified,
`based on channel information. In one aspect of the inven
`tion, modulation and/or coding schemes may be selected on
`a per-stream basis to maximize the aggregate information
`transfer rate while minimizing packet error rates (PER) for
`information transmitted simultaneously via a plurality of RF
`channels. For example, this may entail evaluating the SNR
`performance of individual RF channels, and adapting the
`modulation and/or coding scheme for each RF channel
`based on the SNR performance, and data rate maximization
`criteria. Exemplary measures of signal quality may com
`prise, for example, SNR and PER.
`0022 FIG. 1 is an exemplary block diagram of a trans
`mitter and a receiver in a MIMO system, in accordance with
`an embodiment of the invention. With reference to FIG. 1
`there is shown a transmitter 100 and a receiver 101. The
`transmitter 100 may comprise a coding block 102, a punc
`ture block 104, an interleaver block 106, a plurality of
`mapper blocks 108a, . . . .108n, a plurality of inverse fast
`Fourier transform (IFFT) blocks 110a, . . . .110n, a beam
`forming V matrix block 112, and a plurality of digital to
`analog (D/A) conversion and antenna front end blocks 114a,
`. . . .114n. The receiver 101 may comprise a plurality of
`antenna front end and analog to digital (A/D) conversion
`blocks 116a, . . . .116n, a beam forming U matrix block 118,
`a plurality of fast Fourier transform (FFT) blocks 120a, . . .
`120n, a channel estimates block 122, a plurality of equalizer
`blocks 124a,...,124n, a plurality of demapper blocks 126a,
`... .126n, a deinterleaver block 128, a depuncture block 130,
`and a Viterbi decoder block 132.
`0023 The matrices V and U in beam forming blocks 112
`and 118 respectively refer to matrices utilized in the beam
`forming technique. U.S. application Ser. No.
`(Attor
`
`ney Docket No. 16307US02) filed Feb. 7, 2005, provides a
`detailed description of Eigen beam forming and is hereby
`incorporated herein by reference in its entirety.
`0024.
`In the transmitter 100, the coding block 102 may
`transform received binary input data blocks by applying a
`forward error correction (FEC) technique such as, for
`example, binary convolutional coding (BCC). The applica
`tion of channel coding techniques such as FEC may improve
`the ability to successfully recover transmitted data at a
`receiver by appending redundant information to the input
`data prior to transmission via an RF channel. The ratio of the
`number of bits in the binary input data block to the number
`of bits in the transformed data block may be known as the
`coding rate. The coding rate may be specified using the
`notion, i/t, where t represents the total number of bits
`which comprise a coding group of bits, while is represents
`the number of information bits that are contained in the
`group of bits t. Any number of bits (t-i) may represent
`redundant bits which may enable the receiver 101 to detect
`and correct errors introduced during transmission. Increas
`ing the number of redundant bits may enhance the capabili
`ties at the receiver to detect and correct errors in information
`bits.
`0025 The puncture block 104 may receive transformed
`binary input data blocks from the coding block 102 and alter
`the coding rate by removing redundant bits from the
`received transformed binary input data blocks For example,
`if the coding block 102 implemented a % coding rate, 4 bits
`of data received from the coding block 102 may comprise 2
`information bits, and 2 redundant bits. By eliminating 1 of
`the redundant bits in the group of 4 bits, the puncture block
`104 may adapt the coding rate from 4 to 2/3. The interleaver
`block 106 may rearrange bits received in a coding rate
`adapted data block from the puncture block 104 prior to
`transmission via an RF channel to reduce the probability of
`uncorrectable corruption of data due to burst of errors,
`impacting contiguous bits, during transmission via an RF
`channel. The output from the interleaver block 106 may also
`be divided into a plurality of streams where each stream may
`comprise a non-overlapping portion of the bits from the
`received coding rate-adapted data block. Therefore, for a
`given number of bits in the coding rate-adapted data block,
`ba, a given number of streams from the interleaver block
`106, n, and a given number of bits assigned to an individual
`stream i by the interleaver block 106, b(i):
`
`st
`
`equation 1
`
`0026. The plurality of mapper blocks 108a,....108n may
`comprise a number of individual mapper blocks which is
`equal to the number of individual streams generated by the
`interleaver block 106. Each individual mapper block 108a,
`... 108n may receive a plurality of bits from a correspond
`ing individual stream, mapping those bits into a symbol by
`applying a modulation technique based on a constellation
`utilized to transform the plurality of bits into a signal level
`representing the symbol. The representation of the symbol
`may be a complex quantity comprising in-phase (I) and
`quadrature (Q) components. The mapper block 108a, .
`. .
`
`Exhibit 1032
`Panasonic v. UNM
`IPR2024-00364
`Page 13 of 21
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`US 2006/O 1591.20 A1
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`Jul. 20, 2006
`
`108n for stream i may utilize a modulation technique to map
`a plurality of bits, b(i), into a symbol.
`0027. The plurality of IFFT blocks 110a, . . . .110n may
`receive symbols from the plurality of mapper blocks 108a,
`... 108n where each IFFT block, such as 110a, may receive
`a symbol from a corresponding mapper block, such as 108a.
`Each IFFT block 110a, .
`.
`. .110n may subdivide the
`bandwidth of the RF channel into a plurality of n sub-band
`frequencies to implement orthogonal frequency division
`multiplexing (OFDM), buffering a plurality of received
`symbols equal to the number of sub-bands. Each buffered
`symbol may be modulated by a carrier signal whose fre
`quency is based on one of the sub-bands. Each of the IFFT
`blocks 110a, .
`. . .110n may then independently sum their
`respective buffered and modulated symbols across the fre
`quency sub-bands to perform an n-point IFFT thereby gen
`erating a composite OFDM signal.
`0028. The beam forming V matrix block 112 may apply
`the beam forming technique to the plurality of composite
`OFDM signals, or spatial modes, generated from the plu
`rality of IFFT blocks 110a, . . . .110n. The beamforming V
`matrix block 112 may generate a plurality of signals where
`the number of signals generated may be equal to the number
`of transmitting antenna at the transmitter 100. Each of the
`plurality of signals generated by the beam forming V block
`112 may comprise a weighted Sum of at least one of the
`received composite OFDM signals from the IFFT blocks
`110a, . . . .110n. The plurality of D to A conversion and
`antenna front end blocks 114a, . . . .114n may receive the
`plurality of signals generated by the beam forming V matrix
`block 112, and convert the digital signal representation
`received from the beam forming V matrix block 112 to an
`analog RF signal which may be amplified and transmitted
`via an antenna. The plurality of D to A conversion and
`antenna front end blocks 114a, . . . .114n may be equal to the
`number of transmitting antenna at the transmitter 100. Each
`D to A conversion and antenna front end block 114a, . . .
`114n may receive one of the plurality of signals from the
`beam forming V matrix block 112 and may utilize an antenna
`to transmit one RF signal via an RF channel.
`0029. In the receiver 101, the plurality antenna front end
`and A to D conversion blocks 116a, . . . .116n may receive
`analog RF signals via an antenna, converting the RF signal
`to baseband and generating a digital equivalent of the
`received analog baseband signal. The digital representation
`may be a complex quantity comprising I and Q components.
`The number of antenna front end and A and D conversion
`blocks 116a, .
`.
`. .116n may be equal to the number of
`receiving antenna at the receiver 101. The beam forming U*
`block 118 may apply the beam forming technique to the
`plurality of digital signals received from the plurality of
`antenna front end and A and D conversion blocks 116a, . .
`. 116n. The beam forming U* block 118 may generate a
`plurality of signals where the number of signals generated
`may be equal to the number of streams utilized in generating
`the signals at the transmitter 100. Each signal in the plurality
`generated by the beam forming U* block 118 may comprise
`a weighted Sum of at least one of the digital signals received
`from the antenna front end and A to D conversion blocks
`116a, . . . .116n. The plurality of FFT blocks 120a, . . . .120n
`may receive a plurality of signals, or spatial modes, from the
`beam forming U* block 118. The plurality of FFT blocks
`120a, .
`.
`. .120n may be equal to the number of signals
`
`generated by the beam forming U* block 118. Each FFT
`block 120a, .
`.
`. .120n may receive a signal from the
`beam forming U* block 118, independently applying an
`n-point FFT technique, demodulating the signal by a plu
`rality of carrier signals based on the n Sub-band frequencies
`utilized in the transmitter 100. The demodulated signals may
`be mathematically integrated over one Sub band frequency
`period by each of the plurality of FFT blocks 120a, . . . .120n
`to extract the n symbols contained in each of the plurality of
`OFDM signals received by the receiver 101.
`0030 The channel estimates block 122 may utilize pre
`amble information contained in a received RF signal to
`compute channel estimates. The plurality of equalizer blocks
`124a, .
`.
`. .124n may receive symbols generated by the
`plurality of FFT blocks 120a, .
`.
`. .120n. The plurality of
`equalizer blocks 124a, . . . .124n may be equal to the number
`of FFT blocks 120a, . . . .120n. Each of the equalizer blocks
`124a, . . . .124n may receive a signal from one of the FFT
`blocks 120a, . . . .120n, independently processing the signal
`based on input from the channel estimates block 122 to
`recover the symbol originally generated by the transmitter
`100. Each equalizer block 124a, .
`. . .124n may comprise
`Suitable logic, circuitry, and/or code that may be adapted to
`transform symbols received from an FFT block 120a, . . .
`120n to compensate for fading in the RF channel. The
`plurality of demapper blocks 126a. . . . .126n may receive
`symbols from the plurality of equalizer blocks 124a, .
`.
`.
`124n. Each in the plurality of demapper blocks 126a. . . .
`126n may reverse map each symbol to a plurality of bits by
`applying a demodulation technique, based on the modula
`tion technique utilized in generating the symbol at the
`transmitter 100, to transform the symbol into a plurality of
`bits. The plurality of demapper blocks 126a. . . . .126n may
`be equal to the number of equalizer blocks 124a, . . . .124n,
`which may also be equal to the number of streams in the
`transmitter 100.
`0031. The deinterleaver block 128 may receive a plurality
`of bits from each of the demapper blocks 126a. . . . .126n,
`rearranging the order of bits among the received plurality of
`bits. The deinterleaver block 128 may rearrange the order of
`bits from the plurality of demapper blocks 126a. . . . .126n
`in, for example, the reverse order of that utilized by the
`interleaver 106 in the transmitter 100. The depuncture block
`130 may insert null bits into the output data block received
`from the deinterleaver block 128 that were removed by the
`puncture block 104. The Viterbi decoder block 132 may
`decode a depunctured output data block, applying a decod
`ing technique which may recover the binary data blocks that
`were input to the coding block 102.
`0032 FIG. 2 is an exemplary block diagram of a trans
`mitter with adaptive modulation and a corresponding
`receiver with adaptive demodulation for a MIMO system, in
`accordance with an embodiment of the invention. With
`reference to FIG. 2 there is shown a transmitter 200, and a
`receiver 201. The transmitter 200 may comprise a transmit
`modulation control block 236, and a plurality of blocks as
`shown in the transmitter 100 (FIG. 1), the coding block 102.
`the puncture block 104, the interleaver block 106, the
`plurality of mapper blocks 108a, . . . .108n, the plurality of
`IFFT blocks 110a, .
`.
`. .110n, the beam forming V matrix
`block 112, and the plurality of digital to analog conversion
`and antenna front end blocks 114a, . . . .114n. The receiver
`201 may comprise a receive demodulation control block
`
`Exhibit 1032
`Panasonic v. UNM
`IPR2024-00364
`Page 14 of 21
`
`

`

`US 2006/O 1591.20 A1
`
`Jul. 20, 2006
`
`234, and a plurality of blocks as shown in the receiver 101
`(FIG. 1), the plurality of antenna front end and digital to
`analog conversion blocks 116a, . . . .116n, the beam forming
`U* matrix block 118, the plurality of FFT blocks 120a, . . .
`120n, the channel estimates block 122, the plurality of
`equalizer blocks 124a, . . . .124n, the plurality of demapper
`blocks 126a, . . . .126n, the deinterleaver block 128, the
`depuncture block 130, and the Viterbi decoder block 132.
`The transmit modulation control block 236 may enable
`control over the selection of modulation techniques utilized
`in the transmitter 200. The receive demodulation control
`block 234 may enable control over the selection of demodu
`lation techniques utilized in the receiver 201. In operation,
`the transmit modulation control block 236 may enable
`control of modulation techniques applied by each of the
`plurality of mapper blocks 108a ... 108n individually, on a
`per-stream basis. The receive demodulation control block
`234 may enable control of demodulation techniques applied
`by each of the plurality of demapper blocks 126a. . . . .126n
`individually, on a per-stream basis.
`0033. In operation, per-stream control of the mapper
`blocks 108a, .
`. . .108n may control the number of bits
`assigned to one or more individual streams, b(i), to ensure
`that the sum of bits across the plurality of streams equals the
`aggregate number of bits in the coding rate-adapted data
`block, b, as shown in equation1.
`0034 FIG. 3 is an exemplary block diagram of a trans
`mitter with adaptive modulation and coding, and a corre
`sponding receiver with adaptive demodulation and decoding
`for a MIMO system, in accordance with an embodiment of
`the invention. With reference to FIG. 3 there is shown a
`transmitter 300, and a receiver 301. The transmitter 300 may
`comprise a plurality of puncture blocks 304a, . . . .304n, a
`plurality of interleaver blocks 306a, . . . .306n, a transmit
`coding control block 340, and a plurality of blocks as shown
`in the transmitter 200 (FIG. 2), the coding block 102, the
`puncture block 104, the interleaver block 106, the plurality
`of mapper blocks 108a, . . . .108n, the plurality of IFFT
`blocks 110a, ... 110n, the beam forming V matrix block 112,
`and the plurality of digital to analog conversion and antenna
`front end blocks 114a, . . . .114n, and the transmit modula
`tion control block 236. The receiver 301 may comprise a
`plurality of deinterleaver blocks 328a, . . . .328n, a plurality
`of depuncture blocks 330a, . .
`. .330n, a receive coding
`control block 338, and a plurality of blocks as shown in the
`receiver 201 (FIG. 2), the plurality of antenna front end and
`digital to analog conversion blocks 116a, .
`.
`. .116n, the
`beam forming U* matrix block 118, the plurality of FFT
`blocks 120a, . . . .120n, the channel estimates block 122, the
`plurality of equalizer blocks 124a, . . . .124n, the plurality of
`demapper blocks 126a, . .
`. .126n, the deinterleaver block
`128, the depuncture block 130, and the Viterbi decoder block
`132, and the receive demodulation control block 234.
`0035) In the transmitter 300, puncture and interleaving
`may be performed individually on a per-stream basis. The
`output from the plurality of puncture blocks 304a, . . . .304n
`may be communicated to the plurality of interleaver blocks
`306a, . . . .306 n. Each puncture block in the plurality 304a,
`. . . .304n may communicate its output to a corresponding
`one of the plurality of interleaver blocks 306a, . . . .306n. The
`output from the plurality of interleaver blocks 306a, .
`.
`.
`306n may be communicated to the plurality of mapper
`blocks 108a, . . . .108n. Each of the plurality of interleaver
`
`blocks 306a, . . . .306n may communicate its output to a
`corresponding one of the plurality of mapper blocks 108a, .
`...108n. The transmit coding control block 340 may enable
`control over the application of puncture utilized in the
`transmitter 300.
`0036). In the receiver 301, depuncture and deinterleaving
`may be performed individually on a per-stream basis. Each
`deinterleaver block 328a, . . . .328in may receive input from
`a plurality of demapper blocks 126a. .
`. . .126n with each
`deinterleaver block in the plurality 328a, . . . .328n receiving
`input from a corresponding one of the plurality of demapper
`blocks 126a. . . . .126 n. Each depuncture block 330a, . . .
`330n may receive input from a plurality of deinterleaver
`blocks 328a, . . . .328n with each depuncture block in the
`plurality 330a, . . . .330n receiving input from a correspond
`ing one of the plurality of deinterleaver blocks 328a, .
`.
`.
`328in. The output from each of the plurality of depuncture
`blocks 330a, . . . .330n may be communicated to the Viterbi
`decoder block 132. The receive decoding control block 338
`may enable control over the application of depuncture
`utilized in the receiver 301.
`0037. In operation, the transmit coding control block 340
`may enable control of puncture applied by each of the
`plurality of puncture blocks 304a, . . . .304n individually, on
`a per-stream basis. The per-stream control of puncture may
`enable the coding rate to vary on a per-stream basis. The
`receive coding control block 338 may enable control of
`depuncture applied by each of the plurality of depuncture
`blocks 330a, . . . .330n individually, on a per-stream basis.
`The per-stream control of depuncture may enable the
`receiver 301 to adapt to differences in the coding rate of the
`received signal on a per-stream basis.
`0038. The ability for a transmitter 200 or 300 and a
`receiver 201 or 301 to coordinate modulation/demodulation
`control and/or coding/decoding control may require closed
`loop feedback mechanisms which enable information
`exchange between a transmitter 200 or 300 and a receiver
`201 or 301. U.S. application Ser. No.
`(Attorney
`Docket No. 16354US02) filed Feb. 7, 2005, provides a
`detailed description of closed loop feedback mechanisms,
`and is hereby incorporated herein by reference in its entirety.
`0039. In an embodiment of the invention, maximizing the
`aggregate data rate via a plurality of RF channels from a
`transmitter 200 may be achieved via adaptive modulation on
`a per-stream basis where the coding rate is the same for all
`streams. This may comprise assigning individual values,
`b(i), for each stream i to maximize the number of data
`block bits, b, which may be transmitted per unit of time
`while achieving a target packet error rate (PER).
`0040. In another embodiment of the invention, maximiz
`ing the aggregate data rate via a plurality of RF channels
`from a transmitter 300 may be achieved via adaptive modu
`lation on a per-stream basis and adaptive coding on a
`per-stream basis. This may comprise assigning individual
`values, b(i), for each stream i, and assigning coding rates
`for each steam to modify the number of information bits,
`i(i) on a per-stream basis. Per-stream control of coding rates
`in addition to modulation rates may provide another variable
`which may be utilized to maximize the number of data block
`bits, b, which may be transmitted per unit of time while
`achieving a PER.
`0041 Various embodiments of the invention which may
`incorporate closed loop feedback mechanisms may adap
`
`Exhibit 1032
`Panasonic v. UNM
`IPR2024-00364
`Page 15 of 21
`
`

`

`US 2006/O 1591.20 A1
`
`Jul. 20, 2006
`
`tively modify coding rates and/or modulation technique in
`response to RF channel fading.
`0042. In an exemplary embodiment of the invention in
`which aggregate data rates may be maximized utilizing
`per-stream modulation control and demodulation control, a
`two step process, for example, may be followed. In the first
`step, bit assignments, b(i), may be computed based on SNR
`values. This may produce graphs indicating a frontier of
`possible values of b(i) for ranges of values of SNR. In a
`second exemplary step, a specific value, b(i), may be
`selected based on an observed SNR and an observed PER.
`0043. In operation, symbols may be transmitted utilizing
`a plurality of tones via an RF channel, where each tone may
`be transmitted at a frequency selected from a range of
`f