(12) United States Patent
`Jeon et al.
`
`USOO6222412B1
`US 6,222,412 B1
`(10) Patent No.:
`*Apr. 24, 2001
`(45) Date of Patent:
`
`(54) CIRCUIT FOR CONTROLLING WAVEFORM
`DISTORTION AT A CONTROL TERMINAL
`OF A RADIO FREQUENCY TRANSISTOR
`(75) Inventors: Kye-Ik Jeon; Jae-Myoung Baek;
`Dong-Wook Kim; Song-Cheol Hong,
`all of Taejon (KR)
`(73) Assignee: Korea Advanced Institute of Science
`and Technology (KR)
`This patent issued on a continued pros
`ecution application filed under 37 CFR
`1.53(d), and is subject to the twenty year
`patent term provisions of 35 U.S.C.
`154(a)(2).
`Subject to any disclaimer, the term of this
`patent is extended or adjusted under 35
`U.S.C. 154(b) by 0 days.
`
`(*) Notice:
`
`(21) Appl. No.: 08/960,640
`(22) Filed:
`Oct. 30, 1997
`(30)
`Foreign Application Priority Data
`Oct. 30, 1996
`(KR) ................................................. 96-49.982
`(51) Int. Cl." ........................................................ H03L 5700
`(52) U.S. Cl. ..................
`327/320, 327/314; 327/325
`(58) Field of Search ..................................... 327/309, 314,
`327/318,320, 325, 326, 586
`
`(56)
`
`References Cited
`
`U.S. PATENT DOCUMENTS
`4,551,643 * 11/1985 Russell et al. ....................... 327/428
`4,553,082 * 11/1985 Nesler ...............
`... 323/288
`4,703,286 * 10/1987 Muterspaugh ....
`... 331/117 FE
`4,847,520 * 7/1989 O’Neill et al.....
`... 323/289
`5,041,766 * 8/1991 Fiene et al. ...
`... 31.5/219
`5,061903 * 10/1991 Vasile ................................... 330/311
`
`5,138,285 * 8/1992 Michels .......................... 33 1/116 FE
`5,262,699
`11/1993 Sun et al. ......................... 315/209 R
`5,376,841 * 12/1994 Itakura et al.
`... 327/94
`5,426,334 * 6/1995 Skovmand .
`... 327/427
`5,500,721 * 3/1996 Randall et al.
`355/265
`5,514.935 * 5/1996 Oda et al. ........
`... 315/82
`5,615,094 * 3/1997 Cosentino et al...................... 363/56
`(List continued on next page.)
`OTHER PUBLICATIONS
`K. Yamauchi et al., A Microwave Miniaturized Linearizer
`Using A Parallel Diode, IEEE MTT-S Digest, 1119-1202
`(1997).
`K.-I. Jeon et al., Input Harmonics Control Using Non-Lin
`ear Capacitor in GaAs FET Power amplifier, IEEE MTT-S
`Digest, 817-820 (1997).
`(List continued on next page.)
`Primary Examiner Kenneth B. Wells
`(74) Attorney, Agent, or Firm- Knobbe, Martens, Olson &
`Bear, LLP
`ABSTRACT
`(57)
`The present invention relates to a circuit for controlling
`waveform distortion resulting from nonlinearity of the
`impedance of a control terminal (gate or base) capacitance
`of a transistor, which can be employed in circuits showing
`a nonlinearity performance of high frequency amplifier or
`oscillator. According to the circuit of the invention, the
`waveform distortion can be properly controlled to improve
`the efficiency of power conversion in a high frequency
`circuit employing FET, regardless of the frequency band,
`while assuring a favorable matching of input for the circuit.
`Also, it can provide the reliability of an integrated circuit by
`employing outside Voltage control circuit. Moreover, it can
`be fabricated on a wafer Substrate of FET circuit with an
`inexpensive cost, which affords unrestricted designing of the
`circuit.
`
`38 Claims, 5 Drawing Sheets
`
`Integrated Circuit
`
`
`
`Outside Voltage
`Control Circuit
`
`Wdiode
`
`VR1
`
`(-)Vsupply
`
`Page 1 of 11
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`GOOGLE EXHIBIT 1005
`
`

`

`US 6,222,412 B1
`Page 2
`
`K. Yamauchi et al., A Novel Series Diode Linearizer for
`U.S. PATENT DOCUMENTS
`Mobile Radio Power Amplifiers, IEEE MTT-S Digest,
`6/1997 Lebbolo ................................. 36184
`5,642,251
`831–834 (1996).
`5,705,898 * 1/1998 Yamashita et al.
`... 315/308
`5,798,666
`8/1998 Tihanyi ......
`... 327/377
`M. Maeda et al., A High Power and High Efficiency Ampli
`5,808,332 * 9/1998 Kohno et al. ........................ 257/280
`fier with Controlled Second-harmonic Source Impedance,
`OTHER PUBLICATIONS
`P.M. White and T.M. O'Leary, A 50% Efficiency 8W IEEE MTT-S Digest, 579–582 (1995).
`C-Band PHEMT Power MMIC Amplifier, IEEE GaAs IC
`Symp., 277–280 (1995).
`
`* cited by examiner
`
`
`
`Page 2 of 11
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`

`

`U.S. Patent
`
`Apr. 24, 2001
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`Sheet 1 of 5
`
`US 6,222,412 B1
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`Capacitance
`
`
`
`
`
`
`
`Vin
`Input
`Af. Matching
`Port
`
`
`
`
`
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`
`
`
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`
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`R
`a TCning
`Port
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`Page 3 of 11
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`U.S. Patent
`
`Apr. 24, 2001
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`Sheet 2 of 5
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`US 6,222,412 B1
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`
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`
`
`Capacitance
`
`|
`
`S
`
`T ly
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`\\\
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`VBids=Vp
`
`FIG. 4A
`
`PRIOR ART
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`Page 4 of 11
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`U.S. Patent
`
`Apr. 24, 2001
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`Sheet 3 of 5
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`US 6,222,412 B1
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`FIG. 5
`
`VBias-VP ve
`
`
`
`a capacitance
`
`-
`
`V p
`
`V 9 V
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`
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`Capacitance
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`FIG. 7
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`Page 5 of 11
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`U.S. Patent
`
`Apr. 24, 2001
`
`Sheet 4 of 5
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`US 6,222,412 B1
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`ÁIddnsA(+)
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`Page 6 of 11
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`

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`U.S. Patent
`U.S. Patent
`
`Apr.24, 2001
`Apr. 24, 2001
`
`Sheet 5 of 5
`Sheet 5 of 5
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`US 6,222,412 Bl
`US 6,222,412 B1
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`Capacitance
`
`
`
`FIG.9
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`Page 7 of 11
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`

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`1
`CIRCUIT FOR CONTROLLING WAVEFORM
`DISTORTION AT A CONTROL TERMINAL
`OF A RADIO FREQUENCY TRANSISTOR
`FIELD OF THE INVENTION
`The present invention relates to a circuit for controlling
`waveform distortion at a control terminal of high frequency
`transistor, more Specifically, to a circuit for controlling
`waveform distortion resulting from nonlinearity of the
`impedance of a control terminal (gate or base) capacitance
`of a transistor, which can be employed in circuits showing
`a nonlinearity performance of high frequency amplifier or
`oscillator.
`
`BACKGROUND OF THE INVENTION
`In general, gate capacitance means a capacitance applied
`between channel area and gate of FET(field effect
`transistor). Referring to FIG. 1, a typical gate capacitance
`characteristic of FET is depicted. As can be seen in FIG. 1,
`the gate capacitance has a value of C0 above threshold
`voltage(Vt), and at a range of below Vp(sVt), it has a
`remained parasitic capacitance(C1) of about /10 of C0 value,
`which is caused by the rapid reduction of the capacitance
`while free carrier disappeared at the channel area.
`The effects of the gate capacitance characteristics on a
`circuit is described in more detail with references on the
`accompanying drawings, which Show a circuit of a high
`frequency power amplifier employing FET (see: FIG. 2) and
`a pattern of Signal waveform distortion at the gate terminal
`of the power amplifier(see: FIG. 3).
`The circuit depicted in FIG.2 may be operated in a class
`of B, AB or F, where gate bias Voltage is Set around Vp as
`shown in FIG. 1. Referring to FIG. 2, the sine wave
`Signal(Vin) is inputted to an input matching part of the
`power amplifier, while a distorted waveform Such as Vg(t)
`occurs at the gate terminal of FET. This distorted waveform
`is shown more specifically in FIG. 3, where the gate Signal
`waveform Vg(t) is a combined one of the gate bias Voltage
`(Vp) and the gate input signal.
`Referring to FIG. 3, time course of the gate Signal
`waveform Vg(t) is shown, where Vg(t) rapidly changes to a
`Spike at a voltage range(2) lower than Vp, while it changes
`slowly at a voltage range(1) higher than Vp. If the Vp biased
`Sine wave are applied to the gate terminal (G) without any
`distortion, the Voltage above Vp will be applied to the gate
`terminal for a period equivalent to 180 within one cycle of
`the sine wave. However, the waveform distortion shown in
`FIG. 3 does not coincide with the expectation, where the
`Voltage above Vp is applied to the gate terminal longer than
`the expectation. This phenomenon is caused by the change
`of capacitance of the impedance of the gate terminal depend
`ing on the Voltage(see: FIG. 1), while the impedance of the
`input matching part, due to the linearity, remains constant
`regardless of the magnitude of the Signal(see: FIG. 2).
`The degree of waveform distortion is directly related with
`the ratio of C0 and C1(see: FIG. 1): The larger the ratio is,
`the Severer the distortion becomes, and a non-distorted
`waveform which is close to the sine wave is provided, when
`the ratio is near 1. In addition, when the Sine wave without
`any distortion is inputted to the gate of FET FET is turned
`on for a period equivalent to 180 of one cycle. However,
`Since the distorted waveform is actually applied to the gate
`as shown in FIG. 3, FET is turned on more longer than the
`period equivalent to 180.
`Due to the reason illustrated as aboves, the drain(D)
`current becomes overflowed, which results in the drop of the
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`overall efficiency of the amplifier(see: Paul M. White, IEEE
`MTTs, pp.277–230(1994); Masahiro Maeda, IEEE MTTs,
`pp.579–582(1995); Kyeik Jeon, IEEE MTTs, pp.817–820
`(1997)).
`According to the Simulation Studies, the amplifier whose
`gate is operated in a distorted waveform as in FIG. 3,
`requires more D.C. electric power more than that operated
`by the sine wave by the percentage of 30%, which means the
`reduction of the efficiency of about 30%. Therefore, the
`reduction of the efficiency can be prevented by controlling
`or avoiding the waveform distortion. And, the distortion can
`be properly controlled by regulating the ratio, Since the
`distortion depends on the nonlinearity of the gate
`capacitance, i.e., the ratio of the capacitances at the range of
`below and above Vp.
`The nonlinearity of capacitance may affect on the linearity
`of the power amplifier, in addition to the reduction of
`efficiency. At the gate, the Voltage Swing is larger at the
`lower input voltage than that of at the higher input Voltage.
`Moreover, Since the capacitance is nonlinear, the impedance
`of gate may be varied depending on the inputted Voltage,
`which causes the occurrence of So-called “phase distortion',
`by which the phase of output according to the input of the
`amplifier changes depending on the electric power.
`Therefore, if the capacitance of gate remains constant with
`out the dependence of the gate Voltage, the gate impedance
`will have a constant value regardless of the applied Voltage,
`which results in the reduction of the phase distortion.
`In this connection, a method for controlling the distortion
`of the Sine wave by regulating the ratio of the gate capaci
`tance in a range of above and below Vp viewed from the X
`side of FIG. 2 to have a value of approximately 1, has been
`Suggested in the art. This method was realized by employing
`a shunt capacitor(Cs) between the gate terminal and Source
`terminal of FET as in FIG. 4(A) (see: Paul M. White, IEEE
`MTTs, pp.277-280(1994)). This circuit, as can be seen in
`FIG. 4(B), has its merits of relaxing the nonlinearity of the
`gate capacitance by increasing the capacitance at the input
`terminal of FET to the level of Cs. However, the prior art
`circuit is proven to be leSS Satisfactory in the Sense that
`matching of impedance of the amplifier input terminal is
`very difficult, due to the increase of admittance of the input
`terminal of the FET by the increased amount of the gate
`capacitance.
`Under the circumstance, a method which employs a
`circuit Supplemented with a LCSeries circuit between Source
`terminal and gate terminal of FET has been Suggested. This
`circuit, grounded on a fact that the waveform distortion
`shown in FIG. 3 is resulted from the second high frequency
`which is caused mainly by the nonlinearity of the gate
`capacitance, controls the waveforms distortion by locating a
`LC Series circuit which has a characteristic of resonating at
`the Second harmonic frequency, between the Source terminal
`and the gate terminal and then by controlling the component
`of the Second harmonic frequency. However, this method
`also have revealed shortcomings Such that: it can be applied
`only in the circuit with narrow frequency band, because the
`inductance and capacitance should be changed according to
`the Signal frequency applied to FET.
`Accordingly, there are Strong reasons for exploring and
`developing alternative means for controlling waveform dis
`tortion at a gate terminal of FET, while overcoming the
`problem that their operating frequency are rather limited and
`matching of the input impedance is difficult, due to the use
`of linear device Such as capacitor.
`SUMMARY OF THE INVENTION
`In this regard, the present invention developed a circuit
`for controlling waveform distortion at a control terminal of
`
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`US 6,222,412 B1
`
`3
`high frequency transistor by Substituting nonlinear device
`Such as diode for linear device Such as capacitor which has
`been used for controlling the decrease of the efficiency
`resulting from the nonlinearity of gate capacitance of high
`frequency FET circuit. The circuit for controlling waveform
`distortion affords easy matching of input impedance regard
`less of the frequency of the circuit and, can control the
`nonlinearity of the gate capacitance, especially, it can con
`trol the gate capacitance on the outside of an integrated
`circuit.
`A primary object of the present invention is, therefore, to
`provide a circuit for controlling waveform distortion at a
`terminal of high frequency transistor, by employing nonlin
`ear device in order to improve the linearity and efficiency of
`the electric power conversion of the high frequency circuit.
`
`BRIEF DESCRIPTION OF DRAWINGS
`The above and the other objects and features of the
`present invention will become apparent from the following
`description given in conjunction with the accompanying
`drawings, in which:
`FIG. 1 is a graph showing a typical gate capacitance
`characteristic depending on the gate Voltage of a field effect
`transistor (FET).
`FIG. 2 is a Schematic diagram showing a circuit of a high
`frequency power amplifier employing FET.
`FIG. 3 is a graph showing a waveform distortion at the
`transistor gate terminal of the power amplifier of FIG. 2.
`FIG. 4(A) is a schematic diagram showing a circuit for
`controlling the waveform distortion of the prior art, where a
`parallel capacitor is installed at the transistor gate terminal.
`FIG. 4(B) is a graph showing the decrease of the nonlin
`earity which is a characteristic of the gate capacitance by
`employing the circuit of FIG. 4(A).
`FIG. 5 is a Schematic diagram depicting a circuit for
`controlling waveform distortion employing a diode, which is
`one of preferred embodiments of the present invention.
`FIG. 6 is a graph showing a typical gate capacitance
`characteristic where nonlinearity is controlled by employing
`the circuit of FIG. 5.
`FIG. 7 is a graph showing the change of the typical gate
`capacitance characteristic depending on the change of the
`junction area of the diode employed in the circuit of FIG. 5.
`FIGS. 8(A) and 8(B) are the other embodiment of a circuit
`which controls the gate capacitance of a transistor on the
`outside of an integrated circuit.
`FIG. 9 is a graph showing the change of the gate capaci
`tance characteristic depending on the Voltage of a diode in
`the circuit of FIG. 8(A).
`DETAILED DESCRIPTION OF THE
`INVENTION
`FIG. 5 is a Schematic diagram depicting a circuit for
`controlling waveform distortion employing a diode, which is
`one of preferred embodiments of the present invention. FIG.
`6 is a graph showing a typical gate capacitance characteristic
`where nonlinearity is controlled by employing the circuit of
`FIG. 5. FIG. 7 is a graph showing the change of the typical
`gate capacitance characteristic depending on the change of
`the junction area of the diode employed in the circuit of FIG.
`5.
`Referring to FIG. 5, cathode of a diode(D1) is connected
`to a gate terminal of FET, where the diode may be connected
`to a circuit consisted of discrete FET by employing PCB or
`
`4
`may be fabricated in a form of connecting a Source electrode
`and a drain electrode of FET. The diode can be fabricated on
`a wafer substrate in the course of fabricating FET integrated
`circuit.
`Gate terminal of FET Q1 is anode of a diode fabricated by
`a gate-Source junction, while cathode of the diode(D1) is
`connected to the gate terminal of Q1. Therefore, when the
`anode voltage of D1(Vdiode) is 2-Vp(i.e., 2 times of the gate
`bias Voltage), the gate capacitance of Q1 is represented as a
`solid line(63) of FIG. 6. Referring to FIG. 6, a curve 61
`represents a capacitance of the gate-Source junction, while
`the other curve 62 represents a capacitance of the diode, and
`the Sum of curve 61 and 62 makes a curve 63. The curve 63
`has a constant value of about C0+C1 in the range of above
`and below the threshold voltage(Vp). While the overall gate
`capacitance is increased in the range of above and below Vp
`by the capacitors(Cs) in parallel, this circuit increases the
`capacitance only below Vp and does not increase the capaci
`tance above Vp. As a result, this circuit controls waveform
`distortion, and, unlike the prior circuits employing the
`capacitors connected in parallel, match of the input can be
`easily realized in this circuit.
`Also, as shown in FIG. 7 which depicts the adjustment of
`the junction area of a diode, the degree of waveform
`distortion can be controlled by regulating the turn-on time of
`transistor within one cycle on the operation of Signal. This
`is due to the change of the capacitance below Vp depending
`on the area when the junction area of diode is changed. In
`FIG. 7, curve 71 represents a gate capacitance when anode
`area of D1 is 2 times larger than gate area of Q1, and curves
`72, 73 and 74 are gate capacitances when anode area of D1
`is 1 time, 0.5 time and 0 time of gate area of Q1, respec
`tively. By changing the junction area of a diode, the curves
`71, 72, 73 and 74 can adjust the turn-on time below 180°,
`180 and above 180, respectively. Such an adjustment of
`turn-on time may be utilized for the optimization of capa
`bility in the course of designing of a circuit(see: Sachihiro
`Toyoda, IEEE MTTS Digest, pp.277–280(1993)).
`The other embodiment of the present invention includes a
`circuit which is capable of changing the gate capacitance of
`an input terminal of FET by changing an anode Voltage of
`a diode(Vdiode). FIGS. 8(A) and 8(B) depict the circuits for
`controlling the gate capacitance of an IC transistor on the
`outside of an integrated circuit.
`Referring to FIGS. 8(A), the circuit comprises: a circuit
`for allotting voltage(outside voltage control circuit) employ
`ing a variable resistor(VR1) connected to anode of a diode
`on the outside of an integrated circuit; and, a capacitor(Cb)
`is connected to the anode of diode(D1). Referring to FIG.
`8(B), unlike the circuit of FIG. 8(A), cathode of a diode
`(D1) is connected to a gate terminal of FET(Q1') through a
`capacitor(Cb'), while anode of diode(D1) is connected to a
`circuit for allotting voltage through a blocking resistor(Rb").
`The circuit shown in FIG. 8(A) uses a negative voltage
`power, while the circuit of FIG. 8(B) uses a positive voltage
`power. The variable resistors(VR1, VR1') employed in the
`circuits for allotting voltage in FIGS. 8(A) and 8(B) play a
`role of changing the capacitance of each diode by adjusting
`the voltage of each power Supply(VSupply) and applying it
`to anode of diode(D1) and cathode of diode(D1), respec
`tively. The larger the capacitance of capacitors(Cb1, Cb1"),
`the better it is, and operation is not affected, if the capaci
`tance is 4 or 5 times larger than the maximized capacitance
`of diodes(D1, D1'). On the other hand, the blocking resistor
`(Rb") shown in FIG. 8(B) plays a role of blocking alternating
`current(AC) component on line B, whose resistance is
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`S
`preferably fixed as numbers of kohm. AS explained above,
`Since there exists only direct current(DC) component at lines
`A and B, the capacitance of the gate terminal can be
`regulated by installing the variable resistors(VR1, VR1') on
`the outside of the high frequency circuit(integrated circuit),
`So that the circuit of interest can have a proper capability.
`FIG. 9 is a graph showing the change of the characteristic
`gate capacitance depending on Vdiode of the circuit of FIG.
`8(A), where the ratio of junction area of diode and FET gate
`is Set to be 1:1. AS previously described, the gate capacitance
`has the following characteristics depending on the value of
`Vdiode: when Vdiode is 2 Vp, it has a characteristic of curve
`94; when Vdiode is below 2 Vp(around 4 Vp), it has a
`characteristic of curve 91; when Vdiode is between 2 Vp and
`4 Vp(around 3 Vp), it has a characteristic of curves 92 and
`93; and, when Vdiode is above 2 Vp, it has a characteristic
`of curve 95.
`For the reasons provided in the foregoing, the waveform
`distortion Swinging between V1 and V2 can be properly
`controlled, Since the capacitance below Vp can be regulated
`depending on the voltage(see: FIG. 9). The circuit of FIG.
`8(B) (“the circuit 8(B)”) can be understood similarly as in
`the circuit of FIG. 8(A) (“the circuit 8(A)"). For example,
`the circuit 8(B) is operated in an analogous manner as in the
`circuit 8(A) in which Vdiode is 2 Vp, provided that Vdiode
`of the circuit 8(B) is -Vp and gate bias voltage(Vbias) is
`Vp(generally, negative voltage).
`AS clearly illustrated and demonstrated as above, the
`present invention provides a circuit for controlling wave
`form distortion at a control terminal of high frequency
`transistor. According to the circuit of the invention, the
`waveform distortion can be properly controlled to improve
`the efficiency of power conversion in a high frequency
`circuit employing FET, regardless of the frequency band,
`while assuring a favorable matching of input for the circuit.
`Also, it can provide the reliability of an integrated circuit by
`employing outside Voltage control circuit. Moreover, it can
`be fabricated on a wafer Substrate of FET circuit with an
`inexpensive cost, which affords unrestricted designing of the
`circuit.
`Although the preferred embodiment of the present inven
`tion have been disclosed for illustrative purpose, those who
`are Skilled in the art will appreciate that various
`modifications, additions and Substitutions are possible, with
`out departing from the Scope and Spirit of the invention as
`disclosed in the accompanying claims. In particular, though
`the present invention is described in view of MESFET and
`HEMT, it can be applied to transistors including BJT and
`HBT.
`What is claimed is:
`1. A circuit for controlling waveform distortion at a
`control terminal of a transistor which receives a radio
`frequency Signal, the circuit comprising:
`a diode comprising a cathode and an anode, the cathode
`being connected to a control terminal of the transistor
`receiving a radio frequency Signal and the anode being
`provided with a non-Zero fixed voltage during opera
`tion of the circuit;
`a Voltage dividing circuit, connected to the anode of the
`diode, for varying a capacitance of the diode, and
`a capacitor whose one terminal is connected to the anode
`of the diode and the other terminal is grounded.
`2. A circuit for controlling waveform distortion at a
`control terminal of a transistor which receives a radio
`frequency Signal, the circuit comprising:
`a capacitor whose one terminal is connected to the control
`terminal of the transistor,
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`6
`a diode comprising a cathode and an anode, the cathode
`being connected to another terminal of the capacitor
`and the anode being grounded during the operation of
`the circuit,
`a resistor whose one terminal is connected to the cathode
`of the diode, and
`an adjustable Voltage Supply connected to another termi
`nal of the resistor.
`3. A waveform control circuit comprising:
`a transistor receiving a radio frequency Signal at a control
`terminal during operation;
`a first Voltage Supply providing a bias Voltage to the
`control terminal of the transistor;
`a nonlinear device having a first terminal and a Second
`terminal, the nonlinear device having a nonlinear
`capacitance which varies in relation to an applied
`Voltage between the first and Second terminals thereof,
`the first terminal being connected to the control termi
`nal of the transistor, the Second terminal being provided
`with a fixed voltage during operation of the circuit; and
`an adjustable Second Voltage Supply connected to either
`the first or the second terminal of the nonlinear device.
`4. The waveform control circuit as defined in claim 3,
`wherein the transistor comprises one Selected from the group
`consisting of BJT, FET, MESFET, HEMT, and HBT.
`5. The waveform control circuit as defined in claim 3,
`wherein the nonlinear device is a diode, the first terminal is
`a cathode of the diode and the Second terminal is an anode
`of the diode.
`6. The waveform control circuit as defined in claim 3,
`wherein the nonlinear device is connected to the control
`terminal of the transistor via a printed circuit board or an
`integrated circuit.
`7. The waveform control circuit as defined in claim 3,
`further comprising:
`an AC bypass circuit connected to the Second terminal of
`the nonlinear device, the AC bypass circuit bypassing
`an alternating current component of the Signal passing
`through the device from the control terminal of the
`transistor, and
`wherein the adjustable Second Voltage Supply is connected
`to the Second terminal of the nonlinear device and
`provides the fixed voltage to the Second terminal of the
`device during the operation of the circuit.
`8. The waveform control circuit as defined in claim 7,
`wherein the adjustable Second Voltage Supply comprises a
`Voltage dividing circuit.
`9. The waveform control circuit as defined in claim 7,
`wherein the nonlinear device is fabricated within a package
`of an integrated circuit incorporating the transistor whereas
`the adjustable Second Voltage Supply is located outside of the
`package.
`10. The waveform control circuit as defined in claim 7,
`wherein the AC bypass circuit comprises a capacitor.
`11. The waveform control circuit as defined in claim 10,
`wherein the capacitor has a capacitance greater than four
`times the maximum capacitance of the nonlinear device.
`12. The waveform control circuit as defined in claim 3,
`wherein the Second terminal of the nonlinear device is
`grounded, the waveform control circuit further comprising:
`a DC blocking circuit interveningly connecting the first
`terminal of the nonlinear device and the control termi
`nal of the transistor, the DC blocking circuit preventing
`a direct current component of the Signal from being
`applied to the first terminal of the nonlinear device; and
`wherein the adjustable Second Voltage Supply is connected
`to the first terminal of the nonlinear device, the Second
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`US 6,222,412 B1
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`7
`Voltage Supply provides a constant Voltage to the first
`terminal of the device during the operation of the
`circuit.
`13. The waveform control circuit as defined in claim 12,
`wherein the adjustable Second Voltage Supply comprises a
`Voltage dividing circuit.
`14. The waveform control circuit as defined in claim 13,
`wherein an AC blocking circuit interveningly connects the
`Voltage dividing circuit and the first terminal of the device
`to block an alternating current component of the Signal
`flowing through to the Voltage dividing circuit.
`15. The waveform control circuit as defined in claim 14,
`wherein the AC blocking circuit comprises a resistor.
`16. The waveform control circuit as defined in claim 12,
`wherein the nonlinear device is fabricated within a package
`of an integrated circuit incorporating the transistor whereas
`the adjustable Second Voltage Supply is located outside of the
`package.
`17. The waveform control circuit as defined in claim 12,
`wherein the DC blocking circuit comprises a capacitor.
`18. The waveform control circuit as defined in claim 17,
`wherein the capacitor has a capacitance greater than four
`times the maximum capacitance of the nonlinear device.
`19. A method of controlling waveform at a control ter
`minal of a transistor receiving a radio frequency Signal, the
`method comprising:
`providing a first Voltage Supply applying a bias Voltage to
`the control terminal of the transistor;
`providing a nonlinear device having a first terminal and a
`Second terminal, the nonlinear device having a nonlin
`ear capacitance which varies in relation to an applied
`Voltage, the first terminal being connected to the con
`trol terminal of the transistor;
`providing a Second Voltage Supply connected to either the
`first or the Second terminal of the nonlinear device; and
`adjusting the capacitance of the nonlinear device, wherein
`the Second terminal is provided with a fixed voltage
`while the transistor receives a radio frequency Signal.
`20. The method as defined in claim 19, wherein the
`adjusting the capacitance of the nonlinear device comprises
`adjusting the Second Voltage Supply.
`21. The method as defined in claim 19, wherein the
`nonlinear circuit device is a diode, the first terminal is a
`cathode of the diode and the Second terminal is an anode of
`the diode.
`22. The method as defined in claim 21, wherein the diode
`is formed either in a discrete circuit element or as a part of
`an integrated circuit.
`23. The method as defined in claim 21, wherein the
`adjusting the capacitance of the diode comprises adjusting a
`junction area of the diode.
`24. The method as defined in claim 19, wherein the
`transistor comprises a bipolar junction transistor (BJT) or a
`field effect transistor (FET).
`25. The method as defined in claim 20, further compris
`ing:
`providing an AC bypass circuit connected to the Second
`terminal of the nonlinear device, the AC bypass circuit
`
`15
`
`25
`
`35
`
`40
`
`45
`
`50
`
`55
`
`8
`bypassing an alternating current component of the
`Signal passing through the device from the control
`terminal of the transistor, and
`wherein the Second Voltage Supply is connected to the
`Second terminal of the nonlinear device and provides
`the fixed Voltage to the Second terminal of the device.
`26. The method as defined in claim 25, wherein the
`Second Voltage Supply adjusts the fixed voltage applied to
`the Second terminal of the nonlinear device.
`27. The method as defined in claim 26, wherein the
`Second Voltage Supply comprises a Voltage dividing circuit.
`28. The method as defined in claim 25, wherein the
`nonlinear device is fabricated within a package of an inte
`grated circuit incorporating the transistor whereas the Sec
`ond Voltage Supply is provided outside the package.
`29. The method as defined in claim 25, wherein the AC
`bypass circuit comprises a capacitor.
`30. The method as defined in claim 29, wherein the
`capacitor has a capacitance greater than four times of a
`maximum capacitance of the nonlinear device.
`31. The method as defined in claim 19, the method further
`comprising:
`providing a DC blocking circuit interveningly connecting
`the first terminal of the nonlinear device and the control
`terminal of the transistor, the DC blocking circuit
`preventing a direct current component of the Signal
`from being applied to the first terminal of the nonlinear
`circuit device; and
`wherein the Second terminal of the nonlinear device is
`grounded, and the Second Voltage Supply is connected
`to the first terminal of the nonlinear device, the Second
`Voltage Supply applying a constant voltage to the first
`terminal of the device.
`32. The method as defined in claim 31, wherein the
`Second Voltage Supply adjusts the constant Voltage applied to
`the first terminal of the nonlinear device to control the
`nonlinear capacitance thereof.
`33. The method as defined in claim 32, wherein the
`Second Voltage Supply comprises a Voltage dividing circuit.
`34. The method as defined in claim 33, further compris
`ing:
`providing an AC blocking circuit interveningly connects
`the Voltage dividing circuit and the first terminal of the
`device to block an alternating current component of the
`Signal flowing through to the Voltage dividing circuit.
`35. The method as defined in claim 34, wherein the AC
`blocking circuit comprises a resistor.
`36. The method as defined in claim 31, wherein the
`nonlinear device is fabricated within a package of an inte
`grated circuit incorporating the transistor whereas the Sec
`ond Voltage Supply is located outside of the package.
`37. The method as defined in claim 31, wherein the DC
`blocking circuit comprises a capacitor.
`38. The method as defined in claim 37, wherein the
`capacitor has a capacitance greater than four times the
`maximum capacitance of the nonlinear device.
`
`k
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`k
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`k
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`k
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`k
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