DECLARATION OF WILLIAM JOHNSON
`
`1.
`
`My name is William Johnson. I am over the age of twenty-one years, of sound
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`mind, and capable of making the statements set forth in this Declaration. I am competent to testify
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`about the matters set forth herein. All the facts and statements contained herein are within my
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`personal knowledge.
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`2.
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`I visited the University of Texas at Austin's Life Science Library ("Life Science
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`Library") located in Austin, Texas 78712 on January 23, 2020 and scanned certain pages from
`
`Digital Modulation Techniques by Fuqin Xiong ("Xiong").
`
`3.
`
`The Life Science Library's call number for Xiong is TK5103.7 X65 2000. The Life
`
`Science Library had one copy of Xiong, which was indexed and shelved as indicated by the Life
`
`Science Library's online catalog, a true and correct copy of which is attached as Appendix A. In
`
`the copy of Xiong, I scanned the cover, the table of contents, the "Date Due" slip, and pages 7-15,
`
`123-129, 136-139, 154-160, 195-201, 342-347, and 422-441. A true and correct copy of these
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`pages from Xiong is attached as Appendix B.
`
`4.
`
`One date stamp on the "Date Due" slip of Xiong states "AUG 18 2000."
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`5.
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`I visited the University of Texas at Austin's McKinney Engineering Library
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`("McKinney") located in Austin, TX 78712 on January 23, 2020 and scanned certain pages from
`
`Wireless Communications: Principles and Practice by Theodore S. Rappaport ("Rappaport").
`
`6.
`
`McKinney's call number for Rappaport is TK5103.2 R37 1995. McKinney had
`
`one copy of Rappaport, which was indexed and shelved as indicated by McKinney 's online
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`catalog, a true and correct copy of which is attached as Appendix C. In the copy of Rappaport, I
`
`scanned the cover, the table of contents, the "Date Due" slip, and pages 197-298. A true and
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`correct copy of these pages from Rappaport is attached as Appendix D.
`
`7.
`
`One date stamp on the "Date Due" slip of Rappaport states "AUG 14 1998."
`
`1
`
`Qualcomm Incorporated
`Exhibit 1035
`Page 1 of 217
`
`

`

`8.
`
`I visited the University of Texas at Austin's Perry-Castatieda Library ("PCL")
`
`located in Austin, TX 78712 on January 23, 2020 and scanned certain pages from Bluetooth:
`
`Connect Without Cables by Jennifer Bray and Charles F. Sturman ("Bray").
`
`9.
`
`PCL's call number for Bray is TK5103.3 B73 2001. PCL had two copies of Bray,
`
`which were indexed and shelved as indicated by PCL's online catalog, a true and correct copy of
`
`which is attached as Appendix E. In the copy of Bray, I scanned the cover, the table of contents,
`
`the "Date Due" slip, and pages 84-86. A true and correct copy of these pages from Bray is attached
`
`as Appendix F.
`
`10.
`
`One date stamp on the "Date Due" slip of Bray states "JUL 12 2001."
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`1 1.
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`I declare under penalty of perjury that the foregoing is true and correct.
`
`Executed on January 23, 2020 in Austin, Texas, U.S.A.
`
`2
`
`Page 2 of 217
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`

`

`APPENDIX A
`
`APPENDIX A
`
`Page 3 of217
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`Page 3 of 217
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`APPENDIX B
`
`APPENDIX B
`
`Page 5 of217
`
`Page 5 of 217
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`

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`
`Page 7 of 217
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`

`

`THE UNIVERSITY OF TEXAS AT AUSTIN
`THE GENERAL LIBRARIES
`
`AUG 2 5 2004
`
`RETURNED
`
`JAN 1 8 2005
`
`AUG 31 2005
`
`JUN 012006
`
`Page 8 of217
`
`Page 8 of 217
`
`

`

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`Page 9 of217
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`

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`lfib‘“‘ : I
`
`RETURNED
`
`AUG 3 o 200:1AU
`
`
`
`JAN 16 2001
`
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`JUN 0 4 20013433. n ENC-\N
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`Page 10 of217
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`Page 10 of 217
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`

`

`Library of Congress Caalosing-in-Publicauon 0m
`Xiong, Fuqin.
`Digital modulation techniques / Fu
`p. cm. — (Am-ch House teleco
`Includes bibliographical references
`ISBN 0-89006-970-0 (alk. paper)
`1. Digital modulation.
`1. Title.
`
`II. Series.
`
`qin Xiong.
`mmunications library)
`and index.
`
`TK5103.7 X65 2000
`621.3815’36—dc21
`
`99-05809]
`CIP
`
`British library Cataloguing in Publication Data
`Xiong, Fuqin
`Digital modulation techniques. — (Artech House
`telecommunications library)
`1. Digital modulation
`I. Title
`
`621.3'81536
`
`ISBN 0-89006070-0
`
`Cover design by Igor Valdman
`
`© 2000 ARTECH HOUSE, INC.
`685 Canton Street
`
`Norwood, MA 02062
`
`All rights reserved. Printed and bound in the United States of America. No part 0‘-
`this book may be reproduced or utilized in any form or by any means. electronic 0'
`mechanical. including photocopying, recording. or by any information storage and I’c‘
`tricval system, without permission in writing from the publisher.
`All terms mentioned in this book that are known to be trademarks or service made
`have been appropriately capitalized. Anech House cannot attest to the accuracy ofthis
`information. Use of a term in this book should not be regarded as affecting (ht valid-
`ity of any trademark or service mark.
`
`International Standard Book Number: 0-89006o970-0
`Library of Congress Catalog Card Number: 99-05809]
`
`1098765432]
`
`Page 110f217
`
`Page 11 of 217
`
`

`

`Contents
`
`Preface
`
`Chapter 1
`
`Introduction
`
`1.1 Digital Communication Systems
`1.2 Communication Channels
`1.2.1 Additive White Gaussian Noise Channel
`1.2.2 Bandlimited Channel
`
`1.2.3 Fading Channel
`1.3 Basic Modulation Methods
`
`1.4 Criteria of Choosing Modulation Schemes
`1.4.1 Power Efficiency
`1.4.2 Bandwidth Efficiency
`1.4.3 System Complexity
`1.5 Overview of Digital Modulation Schemes
`References
`
`Chapter 2
`
`Baseband Modulation (Line Codes)
`2.1 Differential Coding
`2.2 Description of Line Codes
`2.2.1 Nonretum-to-Zero Codes
`2.2.2 Retum-to—Zero Codes
`
`2.2.3 Pseudotemary Codes (including AMI)
`2.2.4 Biphase Codes (including Manchester)
`2.2.5 Delay Modulation (Miller Code)
`Power Spectral Density of Line Codes
`2.3.1 PSD of Nonretum-to-Zero Codes
`2.3.2 PSD of Retum-to-Zero Codes
`
`2.3
`
`2.3.3 PSD of Pseudotemary Codes
`2.3.4 PSD of Biphase Codes
`2.3.5 PSD of Delay Modulation
`
`V
`
`xiii
`
`Oflflobb——
`
`10
`10
`ll
`12
`15
`
`l7
`18
`22
`25
`25
`26
`27
`27
`28
`30
`34
`35
`37
`40
`
`Page 12 of217
`
`| i
`
`Page 12 of 217
`
`

`

`vi
`
`Digital Modulation Techniques
`
`2.5
`
`2.6
`
`2.4 Bit Error Rate of Line Codes
`2.4.! BER of Binary Codes
`2.4.2 BER of Pseudoternary Codes
`2.4.3 BER of Biphase Codes
`2.4.4 BER of Delay Modulation
`Substitution Line Codes
`2.5.1 Binary N-Zero Substitution Codes
`2.5.2 High Density Bipolar n Codes
`Block Line Codes
`2.6.] Coded Mark Inversion Codes
`2.6.2 Differential Mode Inversion Codes
`2.6.3 mBnB Codes
`2.6.4 mBlC Codes
`2.6.5 DmBlM Codes
`2.6.6 PFmB(m+l)B Codes
`2.6.7 anT Codes
`
`2.7
`
`Chapter 3
`
`3.2
`3.3
`3.4
`
`Frequency Shift Keying
`3.!
`Binary FSK
`3.l.l Binary FSK Signal and Modulator
`3.1.2 Power Spectral Density
`Coherent Demodulation and Error Performance
`Noncoherent Demodulation and Error Performance
`M-ary FSK
`3.4.l MPSK Signal and Power Spectral Density
`3.4.2 Modulator, Demodulator. and Error
`Performance
`Demodulation Using Discriminator
`Synchronization
`Summary
`References
`
`3.5
`3.6
`3.7
`
`Chapter 4
`
`Phase Shift Keying
`4.|
`Binary PSK
`4.2
`Differential BPSK
`4.3
`M-ary PSK
`4.4
`PSD of MPSK
`4.5
`Differential MPSK
`4.6
`Quadrature PSK
`
`——'—
`fl,“5
`
`l
`
`Page 13 of217 A
`
`Page 13 of 217
`
`

`

`
`
`Contents
`
`4.7 Differential QPSK
`4.8 Offset QPSK
`4.9
`1t/4-QPSK
`4. l0 Synchronization
`4.10.] Carrier Recovery
`4.10.2 Clock Recovery
`4.10.3 Effects of Phase and Timing Error
`4.1 I Summary
`4.12 Appendix 4A
`References
`
`Chapter 5 Minimum Shift Keying and MSK-Type Modulations
`5.I Description of MSK
`5.] .l MSK Viewed as a Sinusoidal Weighted OQPSK
`5.1.2 MSK Viewed as a Special Case of CPFSK
`Power Spectrum and Bandwidth
`5.2.1 Power Spectral Density of MSK
`5.2.2 Bandwidth of MSK and Comparison with PSK
`5.3 Modulator
`5.4 Demodulator
`
`5.2
`
`5.5 Synchronization
`5.6 Error Probability
`5.7 Serial MSK
`
`5.7.I SMSK Description
`5.7.2 SMSK Modulator
`5.7.3 SMSK Demodulator
`
`5.7.4 Conversion and Matched Filter Implementation
`5.7.5 Synchronization of SMSK
`5.8 MSK-Type Modulation Schemes
`5.9
`Sinusoidal Frequency Shifi Keying
`5. IO Simon‘s Class of Symbol-Shaping Pulses
`5.1 I Rabzel and Pathupathy‘s Symbol-Shaping Pulses
`5. 12 Bazin‘s Class of Symbol-Shaping Pulses
`5. l3 MSK-Type Signal‘s Spectral Main Lobe
`5.14 Summary
`References
`
`Chapter 6
`
`Continuous Phase Modulation
`6.1 Description of CPM
`6. I .1 Various Modulating Pulse Shapes
`6. I .2 Phase and State of the CPM Signal
`
`vii
`
`I60
`I67
`I70
`179
`I79
`I83
`I86
`187
`190
`192
`
`I95
`I96
`196
`20I
`203
`203
`204
`207
`210
`
`214
`216
`219
`
`219
`22I
`223
`
`227
`231
`231
`236
`240
`247
`250
`254
`256
`257
`
`259
`260
`261
`265
`
`Page 14 of217
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`Page 14 of 217
`
`

`

`viii
`
`Digital Modulation Techniques
`
`6.2
`
`6.3
`
`6.5
`
`6.6
`
`6.7
`6.8
`
`.—_4.D‘A—_-————
`
`
`V‘I‘Amt—s—-——'
`
`269
`272
`
`274
`
`6.1.3 Phase Tree and Trellis. State Trellis
`POWer Spectral Density
`62.1 Steps for Calculating PSDs for General CPM
`Signals
`6.2.2 Effects of Pulse Shape. Modulation Index. and
`276
`A Priori Distribution
`277
`6.2.3 PSD ofCPFSK
`279
`MLSD for CPM and Error Probability
`28]
`6.3.! Error Probability and Euclidean Distal"cc
`285
`6.3.2 Comparison of Minimum Distances
`286
`Modulator
`286
`6.4.1 Quadrature Modulator
`292
`6.4.2 Serial Modulator
`295
`6.4.3 All-Digital Modulator
`297
`Demodulator
`297
`6.5.l Optimum ML Coherent Demodulator
`301
`6.5.2 Optimum ML Noncoherent Demodulator
`3| l
`6.5.3 ViterbiDemodulator
`3 l 7
`6.5.4 Reduced-Complexity Viterbi Demodulator
`6.5.5 Reduction of the Number of Filters for LREC CPM 320
`325
`6.5.6 ML Block Detection of Noncoherent CPM
`326
`6.5.7 MSK-Type Demodulator
`330
`6.5.8 Difi‘erential and Discriminator Demodulator
`333
`6.5.9 Other Types of Demodulators
`337
`Synchronization
`337
`6.6.l MSK-Type Synchronizer
`6.6.2 Squaring Loop and Fourth-Power Loop
`Synchronizers
`6.6.3 Other Types of Synchronizer
`Gaussian Minimum Shifl Keying
`Summary
`References
`
`340
`34 l
`342
`346
`347
`
`Chapter 7
`
`Multi-h Continuous Phase Modulation
`7.1
`MHPM Signal. Phase Tree, and Trellis
`7.2
`Power Spectral Density
`7.3
`Distance Properties and Error Probability
`7.4
`Modulator
`7.5
`
`Demodulator and Synchronization
`7.5.] A Simple ML Demodulator for Multi-h Binary
`CPFSK
`
`35|
`351
`36!
`366
`382
`382
`
`382
`
`Page 15 of217
`
`Page 15 of 217
`
`

`

`Contenls
`
`7.5.2 Joint Demodulation and Carrier Synchronization of
`Multi-h CPFSK
`
`7.5.3 Joint Carrier Phase Tracking and Data Detection of
`Multi.h CPFSK
`
`ix
`
`388
`
`392
`
`7.6
`
`7.5.4 Joint Demodulation. Carrier Synchronization. and
`Symbol Synchronization of M-ary Multi-h C PFSK 393
`7.5.5 Synchronization of MHPM
`398
`Improved MHPM Schemes
`399
`7.6.1 MHPM with Asymmetrical Modulation Indexes
`400
`7.6.2 Multi-T Realization of Multi-h Phase Codes
`401
`
`7.6.3 Correlatively Encoded Multi-h Signaling Technique 401
`7.6.4 Nonlinear Multi-h CPFSK
`403
`
`Summary
`7.7
`7.8 Appendix 7A
`References
`
`403
`404
`408
`
`411
`Quadrature Amplitude Modulation
`411
`8.1 M-ary Amplitude Modulation
`412
`8.1.1 Power Spectral Density
`414
`8.1.2 Optimum Detection and Error Probability
`8.1.3 Modulator and Demodulator for Bandpass MAM 418
`8.1.4 On-Off Keying
`421
`8.2 QAM Signal Description
`422
`8.3 QAM Constellations
`425
`8.3.1 Square QAM
`429
`8.4 Power Spectral Density
`432
`8.5 Modulator
`434
`8.6 Demodulator
`436
`
`Chapter 8
`
`8.7 Error Probability
`8.8
`Synchronization
`8.9 Differential Coding in QAM
`8.10 Summary
`8.1 1 Appendix 8A
`References
`
`Chapter 9
`
`Nonconstant-Envelope Bandwidth-Efficient Modulations
`9.1
`Two~Symbol-Period Schemes and Optimum
`Demodulator
`
`9.2 Quasi-Bandlimited Modulation
`9.3 QORC. SQORC, and QOSRC
`9.4
`1JF-OQPSK and TSl-OQPSK
`
`438
`441
`448
`454
`455
`457
`
`459
`
`460
`
`465
`471
`478
`
`Page 16 of217
`
`Page 16 of 217
`
`

`

`Digital Modulation Techniques
`
`10.1.1 Channel Characteristics
`10. I .2 Channel Classification
`10.1.3 Fading Envelope Distributions
`'02 Digital Modulation in Slow. Flat Fading Channels
`10.2.l Rayleigh Fading Channel
`10.2.2 R
`.
`_
`ician Fading Channel
`10.3 Dig
`Ital Modulation in Frequency Selective Channels
`10.4 rt/4-
`DQPSK in Fading Channels
`10.5
`MHPM in Fading Channels
`10.6 QAM in Fading Channels
`10.6.1 Square QAM
`10.6.2 Star QAM
`10.7 R
`emedial Measures Against Fading
`10.8 Summary
`References
`
`Appendix A Power Spectral Densi
`ties of Signals
`A.l
`Bandpass Signals and Spectra
`A.2
`Bandpass Stationary Random Process and PSD
`A.3
`Power Spectral Densities of Digital Signals
`A.3.l Case I: Data Symbols Are Uncol'I‘Clmed
`.
`A.3.2 Case 2: Data Symbols Are Correlated
`Power Spectral Densities of Digital Bandpass signals
`Power Spectral Densities of CPM Signals
`References
`
`AA
`A.5
`
`Appendix B Detection of Signals
`3.1 Detection of Discrete Signals
`B. 1.1 Binary Hypothesis Test
`8.1.2 Decision Criteria
`8.13 M Hypotheses
`Detection of Continuous Signals With Known Phases
`8.2.1 Detection of Binary Signals
`8.2.2 Decision of M-ary Signals
`
`8.2
`
`ii
`
`490
`498
`515
`515
`
`517
`518
`518
`521
`524
`527
`527
`S31
`S33
`
`$48
`554
`555
`558
`560
`563
`564
`
`567
`567
`$69
`572
`574
`S76
`577
`580
`586
`
`589
`589
`589
`590
`594
`596
`596
`608
`
`Page 17 of217
`
`4__________~——
`_v:;.:/':-——.-
`F»!—JE'x-._—'
`
`Page 17 of 217
`
`

`

`Contents
`
`8.3 Detection ofContinuous Signals With Unknown Phases
`8.3.] Receiver Structure
`8.3.2 Receiver Error Performance
`References
`
`Glossary
`About the Author
`Index
`
`xi
`
`615
`615
`621
`625
`
`627
`631
`633
`
`Page 18 of217
`
`Page 18 of 217
`
`

`

`1.1:
`
`Digital Modulation Techniques
`
`Then the probability density function (PDF) of n can be written as
`
`1
`
`2
`
`13(71): WGXP‘I—KTO}
`
`(l9)
`
`annels are approximately an AWGN channel. For ex-
`_
`‘
`ample, the "ne'Of'S'ghl (L03) radio channels. including fixed terrestrial miCI'OWave
`links and fixed satellite links,
`-
`
`In this book, allmodulation schemes are studied for the AWGN channel. The
`fold. First. some channels are approximately an AWGN
`used directly. Second, additive Gaussian noise is ever
`er other channel impairments such as limited bmdwidth.
`.
`.
`fading, multtpath, and other interferences exist or not. Thus the AWGN channel is the
`be“ channel mat 0“ can 861- The performance ofa modulation scheme evaluated in
`this channel is an upper bound on the performance. When other channel impairments
`exist. the system performance will degrade. The extent ofdegradation may vary for
`emes. The performance in AWGN can serve as a standard
`dation and also in evaluating effectiveness of impainnent-
`
`combatttng techniques.
`
`1.2.2
`
`Bandlimited Channel
`
`When the channel bandwidth is smaller than the signal bandwidth. the channel is
`bandlimited. Severe bandwidth limitation causes intersymbol interference (lSl) (i.e..
`digital pulses will extend beyond their transmission duration (symbol period T. )) and
`interfere with the next symbol or even more symbols. The 15! causes an increase
`in the bit error probability (P5) or bit error rate (BER). as it is commonly called.
`When increasing the channel bandwidth is impossible or not cost-efficient. channel
`equalization techniques are used for combatting lSl. Throughout the years. numerous
`equalization techniques have been invented and used. New equalization techniques
`are appearing continuously. We will not cover them in this book. For introductory
`ueatment of equalization techniques. the reader is referred to [LChaptcr 6| or any other
`communication systems books.
`
`Page 19 of217
`
`Page 19 of 217
`
`

`

`Chapter I
`
`Introduction
`
`7
`
`1.2.3
`
`Fading Channel
`
`Fading is a phenomena occurring when the amplitude and phase of a radio signal
`change rapidly over a short period of time or travel distance. Fading is caused by in-
`terference between two or more versions of the transmitted signal which arrive at the
`receiver at slightly different times. These waves, called multipath waves. combine
`at the receiver antenna to give a resultant signal which can vary widely in amplitude
`and phase. If the delays of the multipath signals are longer than a symbol period,
`these multipath signals must be considered as different signals. In this case, we have
`individual multipath signals.
`In mobile communication channels. such as ten'estrial mobile channel and satel-
`lite mobile channel, fading and multipath interference are caused by reflections from
`surrounding buildings and terrains.
`In addition, the relative motion between the
`transmitter and receiver results in random frequency modulation in the signal due
`to different Doppler shifts on each of the multipath components. The motion of
`surrounding objects. such as vehicles, also induces a time-varying Doppler shifl on
`multipath component. However, if the surrounding objects move at a speed less than
`the mobile unit. their effect can be ignored [2].
`Fading and multipath interference also exist in fixed LOS microwave links [3]-
`On clear. calm summer evenings. normal atmospheric turbulence is minimal. The
`troposphere stratifies with inhomogeneous temperature and moisture distributions.
`Layering of the lower atmosphere creates sharp refractive index gradients which in
`turn create multiple signal paths with different relative amplitudes and delays.
`Fading causes amplitude fluctuations and phase variations in received signals.
`Multipath causes intersymbol interference. Doppler shift causes carrier frequency
`drift and signal bandwidth spread. All these lead to performances degradation of
`modulations. Analysis of modulation performances in fading channels is given in
`Chapter I0 where characteristics of fading channels will be discussed in more detail.
`
`I.3
`
`BASIC MODULATION METHODS
`
`Digital modulation is a process that impresses a digital symbol onto a signal suitable
`for transmission. For short distance transmissions, baseband modulation is usually
`
`used. Baseband modulation is often called line coding. A sequence of digital sym-
`bols are used to create a square pulse waveform with certain features which represent
`each type of symbol without ambiguity so that they can be recovered upon reception.
`These features are variations of pulse amplitude, pulse width. and pulse position.
`Figure 1.3 shows several baseband modulation waveforms. The first one is the non-
`return to zero-level (N RZ-L) modulation which represents a symbol I by a positive
`
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`

`

`8
`
`Digital Modulation Techniques
`
`(a) NRZ-L
`
`l
`
`0
`
`l
`
`I
`
`l
`
`0
`
`0
`
`l
`
`-A
`
`(b) Unipolar RZ
`
`A
`
`(c) Bi-Q-L (Manchester)
`A
`
`-A
`
`Figure 1.3 Baseband digital modulation examples.
`
`square pulse with length T and a symbol 0 by a negative square pulse with length T.
`The second one is the unipolar retum to zero modulation with a positive pulse of T0
`for symbol l and nothing for 0. The third is the biphase level or Manchester. alter
`its inventor, modulation which uses a waveform consisting of a positive first-half T
`pulse and a negative second-half T pulse for l and a reversed waveform for 0. These
`and other baseband schemes will be discussed in detail in Chapter 2.
`For long distance and wireless transmissions. bandpass modulation is usually
`used. Bandpass modulation is also called carrier modulation. A sequence of dig-
`ital symbols are used to alter the parameters of a high-frequency sinusoidal signal
`called carrier.
`It is well known that a sinusoidal signal has three parameters: am-
`plitude, frequency, and phase. Thus amplitude modulation. frequency modulation.
`and phase modulation are the three basic modulation methods in passband modula-
`tion. Figure 1.4 shows three basic binary carrier modulations. They are amplitude
`shifl keying (ASK). frequency shift keying (FSK), and phase shift keying (PSK). ln
`ASK, the modulator puts out a burst of carrier for every symbol I. and no signal
`for every symbol 0. This scheme is also called on-ofi' keying (00K). In a general
`ASK scheme. the amplitude for symbol 0 is not necessarily 0.
`In FSK. for symbol
`l a higher frequency burst is transmitted and for symbol 0 a lower frequency burst
`
`Page 21 of217
`
`l
`
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`
`

`

`Chapter I
`
`Inlrvducnon
`
`9
`
`ASK
`
`FSK
`
`PSK
`
`Figure l 4 Three basic bandpass modulation schemes.
`
`In PSK, a symbol 1 is transmitted as a burst of carrier
`is transmitted. or vice versa.
`with 0 initial phase while a symbol 0 is transmitted as a burst of carrier with 180°
`initial phases
`Based on these three basic schemes. a variety of modulation schemes can be de-
`rived from their combinations. For example. by combining two binary PSK (BPSK)
`signals with orthogonal carriers a new scheme called quadrature phase shift keying
`(QPSK) can be generated. By modulating both amplitude and phase of the carrier.
`we can obtain a scheme called quadrature amplitude modulation (QAM), etc.
`
`1.4
`
`CRITERIA OF CHOOSINC MODULATION SCHEMES
`
`The essence of digital modern design is to efficiently transmit digital bits and recover
`them from corruptions from the noise and other channel impairments. There are
`three primary criteria of choosing modulation schemes: power efficiency, bandwidth
`
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`Page 22 of 217
`
`

`

`IO
`
`Digital Modulation Techniques
`
`efficiency, and system complexity.
`
`1.4.1
`
`Power Efficiency
`
`The bit error rate, or bit error probability of a modulation scheme is inversely related
`to Eb/No. the bit energy to noise spectral density ratio. For example. Pb 0f ASK m
`the AWGN channel is given by
`
`
`2E
`
`Pb=Q( Nob)
`
`(1‘10)
`
`where E, is the average bit energy, No is the noise power spectral density (PSDX and
`(2(1) is the Gaussian integral, sometimes referred to as the Q-function. It is defined
`as
`
`0-“)
`Q(x) = /°" LIE—“2dr;
`which is a monotonically decreasing function of 1. Therefore the power efficiency
`of a modulation scheme is defined straightforwardly as the required Eli/Na for a
`certain bit error probability (Pb) over an AWGN channel. Pi, = 10—5 is usually used
`as the reference bit error probability.
`
`1.4.2
`
`Bandwidth Efficiency
`
`The determination of bandwidth efficiency is a bit more complex. The bandwidth
`efficiency is defined as the number of bits per second that can be transmitted In
`one Hertz of system bandwidth. Obviously it depends on the requirement of SYS‘cm
`bandwidth for a certain modulated signal. For example. the one-sided power Specml
`density ofan ASK signal modulated by an equiprobable independent random binary
`sequence is given by
`
`2
`
`mm = A T
`
`A2
`
`varies depending on different criteria. For example" in Figul’:
`al energy concentrates in the band between two nulls,_thuf
`th requrrement seems adequate. Three bandwidth emc'cnc'es
`
`Page 23 of217
`
` ,
`
`‘0'
`
`'——'l
`
`Page 23 of 217
`
`

`

`
`
`Chapter I
`
`Introduction
`
`ll
`
`1
`T
`
`tc -
`
`I
`~
`tc’T
`
`fc
`
`f°++
`
`2
`fo’ T
`
`Figure 1.5 Power spectral density of ASK.
`
`.
`used in the literature are as follows:
`Nyquist Bandwidth Efficiency—Assuming the system uses Nyquis‘ “deal rec'
`tangular) filtering at baseband. which has the minimum bandwidth required for in-
`tersymbol interference-free transmission of digital signals, then the bandWidth at
`baseband is 0_ 512,, R3 is the symbol rate, and the bandwidth at carrier frequency
`is W = R,. Since R, : lib/1082 M, Rb = bit rate, for M-al')’ modulation, the
`bandwidth efficiency is
`
`Rb/W = logz M
`
`(”2)
`
`Null-to—Null Bandwidth Efficiency—For modulation schemes that have power
`density spectral nulls such as the one of ASK in Figure 1.5, defining the bandwidth
`as the width of the main spectral lobe is a convenient way of bandwidth definition.
`Percentage Bandwidth Efficiency—If the spectrum of the modulated signal
`does not have nulls, as in general continuous phase modulation (CPM), null-to—null
`bandwidth no longer exists. In this case. energy percentage bandwidth may be used.
`Usually 99% is used, even though other percentages (e.g., 90%, 95%) are also Used'
`
`1.4.3
`
`System Complexity
`
`System complexity refers to the amount of circuits involved and the technical dif-
`ficu't)’ 0f the system. Associated with the system complexity is the COSt 0f manu—
`
`Page 24 of217
`
`
`
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`
`

`

`l2
`
`Digital Modulation "Techniques
`
`c0"
`
`. r conce
`rse a map
`
`"
`
`.
`in choosmg a mo
`
`facturing, which is of
`dulation tec
`hnique'
`-
`Usually the demodul
`oherent dem°d“'?'
`tor is much more co
`ator is more complex than the modulalgch cmicr recovery is
`mplex than noncoherem demodulatorl orimms like the Viterbi
`required. For some demodulation methOdS' 5°phisnca-Ed :rgnpafison‘
`algorithm isrequired. Allthesearebasis forComplexfl)’:vstem complexi‘)’ are the
`Since powar efiiciency, bandwidth efficiency, andwi'll always pay attention to
`main criteria ofchoosing a modulation teChnigue’ we tofthe book-
`them in the analysis ofmodulation techniques m the res
`d a scriptive
`t.s
`oveavuaworDIGITALM0DULATIONs
`To provide the reader with an overview, we "St-film:fzreiziaT;ble "l and miss:
`names ofvarious digital modulations that we w“ c oftheSchemescanbeSiencan
`them inarelationshiptreediagram inFigure l'6‘ some
`e differential encoding
`from morethan one “parent“ scheme. The “nameswsgoherenilydemOdula‘ed are
`beusedarelabeledbyletterDandthosethatcanbeta,demodula‘ed'
`.
`-
`t
`two
`labeledwithaletterN.Allschemescanbewhere“
`hetree are classified in o
`.
`The modulation schemes listed in ‘he “ableand‘envelope- Underconstfll“ el"t
`large categories: constant envelope and nonconswlgt and CPM- Under nonconslfln
`velope class, there are three subclasses: FSK' PS '
`envelope class.
`there are three subclasses: ASK. QAM. and 0th
`lope modulations.
`Among the listed schemes, ASK. PSK° 3:323:33 s:hemes. The advanced
`MSK. GMSK, CPM, MHPM, andQAM.etc.
`.
`hemeS-
`.
`schemesarevariationsandcombinations021thes:?t:l:|:cf°" communiC3‘_'°“ 3:51:11:
`whoihxvgte‘fxpii‘gtSrspneiust operate in the nonlincaEEfiEy. AnexampleISthe
`1
`class is genera y
`.
`-
`0f the mpu
`.
`characteristic inordertoachievemilxi')“.uma:£::§f:lotettmuni°a‘i°ns- Bowen:?.m!:;
`TX;(ligalzegclhinlasvi:Eltzzltzfareinappropriatefor'Szlggrgfimes. BinaryFSK
`-
`Iifier m 58
`-
`licatlon st
`lgiaveverylowbandwidthefi‘tciency incomparisonWl‘tion cellularsystems. AMPS
`isused inthe low-ratecontrol channels offirst gageguropean total accesscammt;
`(advance mobile phone service ofUS.) and ETAfC AMPS and 8 Kbps for E‘IAC. .
`nication system). The data rates are l0 KbPS 01:8K and MSK have been “53“ m
`The PSKschemes, including BPSK, QPSK. 0Q
`'
`-d 180° abrupt
`satellitecommugglzu‘gvsg’rsthesnpsecialattentionduetoitsabiltlyge‘ajviz'digimlmobile
`h 35:52::chenalbledifferentialdemodulation. “11ml;bfsgDC)system.
`scalar systems such as the United States digital CC ‘1
`
`cHEMEs
`
`. fonS an
`
`e
`
`er noncoltswnt en
`
`ve-
`
`.
`b sic modulations
`
`and
`
`Page 25 of 217
`
`

`

`Chapter I
`
`Introduction
`
`13
`
`Abbreviation
`
`AltcmaIeAbbr
`
`-
`
`;
`
`
`Frequency Shifl Keying (FSk)
`E- Binary Frequency Shift Keying
`— M-ary Frequency Shifl Keying
`
`
`
`
`“——
`manna-—
`
`———
`m— M-ary Pm: Shift Keying
`
`Continuous Phase Modulnions (CPM)
`
`
`
`
`
`
`Single-h (modulation index) Phase Modulation
`ulii-h Phase Modulation
`
`
`
`iU
`
`!83'5
`
`2°82'U7:” (n3
`
`Table l.l Digital modulation schemes (Abbt.=Abbrevietion).
`
`Page 26 of217
`
`Page 26 of 217
`
`

`

`14
`
`Digital Modulation Techniques
`
`Digital Modulations
`
`Constant Envelope
`
`Nonconstam Envelope
`
`m m
`BFSKIIIW
`
`(D)
`
`IREC
`(CPFSK
`.
`_
`. smusondal
`‘h=0.5
`: pulse-shaping
`.
`—>
`.............. MSK
`- ........................ mm
`
`L-l
`
`$
`
`LRC
`
`LSRC
`
`m
`
`I-
`
`TS
`OQPSK
`
`SQAM
`
`m
`
`m
`
`W ""0?“
`.
`(D)
`I
`'
`:
`u
`
`I :
`
`h=0 s —>
`
`(D)
`
`(N)
`
`Can be difl’erentially encoded and decoded
`
`Can be noncohctcntly detected
`
`Figure L6 Digital Modulation Trcc~ Aflcr [4].
`
`Page 27 of217
`
`Page 27 of 217
`
`

`

`Chapter I
`
`Introduction
`
`15
`
`The PSK schemes have constant envelope but discontinuous phase transitions
`from symbol to symbol. The CPM schemes have not only constant envelope, but also
`continuous phase transitions. Thus they have less side lobe energy in their spectra
`in comparison with the PSK schemes. The CPM class includes LREC. LRC. LSRC.
`GMSK, and TFM. Their difi’erences lie in their different frequency pulses which are
`reflected in their names. For example. LREC means the frequency pulse is a rectan-
`gular pulse with a length of L symbol periods. MSK and GMSK are two important
`schemes in C PM class. MSK is a special case of C PFSK, but it also can be derived
`from OQPSK with extra sinusoidal pulse-shaping. MSK has excellent power and
`bandwidth efficiency. its modulator and demodulator are also not too complex. MSK
`has been used in NASA‘s Advanced Communication Technology Satellite (ACTS).
`GMSK has a Gaussian frequency pulse. Thus it can achieve even better bandwidth
`efficiency than MSK. GMSK is used in the US cellular digital packet data (CDPD)
`system and European GSM (global system for mobile communication) system.
`MHPM is worth special attention since it has better error performance than
`single-h CPM by cyclically varying the modulation index h.
`The generic nonconstant envelope schemes, such as ASK and QAM. are gen-
`erally not suitable for systems with nonlinear power amplifiers. However QAM.
`with a large signal constellation. can achieve extremely high bandwidth efi'iciency.
`QAM has been widely used in modems used in telephone networks, such as computer
`modems. QAM can even be considered for satellite systems. In this case, however.
`back-off in TW'llA's input and output power must be provided to ensure the linearity
`of the power amplifier
`The third class under nonconstant envelope modulation includes quite a few
`schemes. These are primarily designed for satellite applications since they have very
`good bandwidth efficiency and the amplitude variation is minimal. All of them ex-
`cept QQPSK are based on 2T, amplitude pulse shaping and their modulator structures
`are similar to that of OQPSK. The scheme Q2PSK is based on four orthogonal car-
`riers.
`
`References
`
`[I]
`
`[2]
`
`[3]
`
`[4]
`
`Proakis. 1., Digital Communication. New Ybrk: McGraw-Hill. 1983.
`
`Rappaport. T.. "ire/es: Communications: Principles and Practice. Upper Saddle River. New
`Jersey: Prentice Hall. l996.
`
`Siller. C .. “Multipath propagation.“ IEEE Communications Magazine. vol. 22. no.2. Feb. I984.
`pp. 6-l5.
`
`Xiong. F.."Modem techniques in satellite communications.” IEEE Communications Magazine.
`vol. 32. no.8. August I994, pp. 84-98.
`
`Page 28 of217
`
`Page 28 of 217
`
`

`

`l22
`
`Digiul Modulation 1mm
`
`
`
`
`costly, most of FSK receivus use noncoherem demodulliou.
`.,
`
`I'ls“New"“mu”efl’Ofpetformanoeofthcnoneohetutrocdxvdl
`tomatofthecohmiona. However thedegmhuontsonlyl
`4‘
`
`exprasiomandcurvcs fordremprobabilitiesueahoptw
`Finally we explored other possible demodulation. The
`‘
`Intorissimpleandefi'lcient. ltisevenbenermmew- '
`
`ulator fat BFSK.
`
`[I] MILK. M1. Sill. 'smormm'uuww‘}
`
`Judy-August. 1965. pp. "65-1189.
`
`
`
`References
`
`’ .'_>
`
`.
`3!
`
`[21 MIL-unnm. mmama—m f
`memmvol. l8.no.....4Augul970pp29$-300
`
`[3] MILE. “mumormmmmwmm'm
`vol29..nollNou|98l...pp1634-l6‘3
`'
`
`[4] M1.E.‘11wyofammfoedWFM.'hRS)uu-W
`I966. pp. fill-1535.
`
`Selocud Blbllognply
`
`
`
`
`, f";
`.
`
`o ma.uw.wmwmcmw.mu.mfik '~ "l
`o mms..mmcmmmmunyammlsfi;"
`o sag]..'mdmmkvdmwmmdwm -.
`MCMMWmIJMJMIWSm4M
`Skin. 3. mnemm. FMadWau.W
`Prentice Hfll. I988.
`
`0
`
`
`
`
`o smmn.x.pmunmmmm.wwmmmu a
`1993.
`
`'
`
`0
`
`I
`
`Suite. E. 0.. ‘Idcdbhl'ypullemiuhnbyAMmdFM'MM
`v01. 38. Nov. I939. pp ”574426.
`\h'n'euJ‘LL,Wmmmmwmmmamw
`Smlmlm
`9
`
`
`
`Page 29 onI%
`
`Page 29 of 217
`
`

`

`Chapter 4
`
`Phase Shift Keying
`
`Phase shift keying (PSK) is a large class of digital modulation schemes. PSK is
`widely used in the communication industry. In this chapter we study each PSK mod-
`ulation scheme in a single section where signal description, power spectral density.
`modulator/demodulator block diagrams, and receiver error performance are all in-
`cluded. First we present coherent binary PSK(BPSK) and its noncoherent coun-
`terpart, differential BPSK (DBPSK), in Sections 4.l and 4.2. Then we discuss in
`Section 4.3 M-ary PSK (MPSK) and its PSD in Section 4.4. The noncoherent ver—
`sion, differential MPSK (DMPSK) is treated in Section 4.5. Vie discuss in great detail
`quadrature PSK (QPSK) and differential QPSK (DQPSK) in Sections 4.6 and 4.7, re-
`spectively. Section 4.8 is a brief discussion of offset QPSK (OQPSK). An important
`variation of QPSK, the 7r/4—DQPSK which has been designated as the American
`standard of the second-generation cellular mobile communications, is given in Sec-
`tion 4.9. Section 4.10 is devoted to carrier and clock recovery. Finally. we summarize
`the chapter with Section 4. l l.
`
`4.1
`
`BINARY PSK
`
`Binary data are represented by two signals with different phases in BPSK. Typically
`these two phases are 0 and 7r. the signals are
`
`31(t) = Acos21rfct. OStST.
`
`for!
`
`32(t) = —A00321rfct. ogtsT.
`
`for0
`
`(4.1)
`
`These signals are called ann'padal. The reason that they are chosen is that they have
`a correlation coefficient of — l, which leads to the minimum error proba